Download LT5560 - 0.01MHz to 4GHz Low Power Active

LT5560
0.01MHz to 4GHz
Low Power Active Mixer
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DESCRIPTIO
FEATURES
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The LT®5560 is a low power, high performance broadband active mixer. This double-balanced mixer can be
driven by a single-ended LO source and requires only
–2dBm of LO power. The balanced design results in
low LO leakage to the output, while the integrated input
amplifier provides excellent LO to IN isolation. The signal ports can be impedance matched to a broad range
of frequencies, which allows the LT5560 to be used as
an up- or down-conversion mixer in a wide variety of
applications.
Up or Downconverting Applications
Noise Figure: 9.3dB Typical at 900MHz Output
Conversion Gain: 2.4dB Typical
IIP3: 9dBm Typical at ICC = 10mA
Adjustable Supply Current: 4mA to 13.4mA
Low LO Drive Level: –2dBm
Single-Ended or Differential LO
High Port-to-Port Isolation
Enable Control with Low Off-State Leakage Current
Single 2.7V to 5V Supply
Small 3mm × 3mm DFN Package
The LT5560 is characterized with a supply current of 10mA;
however, the DC current is adjustable, which allows the
performance to be optimized for each application with a
single resistor. For example, when biased at its maximum
supply current (13.4mA), the typical upconverting mixer
IIP3 is +10.8dBm for a 900MHz output.
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APPLICATIO S
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Portable Wireless
CATV/DBS Receivers
WiMAX Radios
PHS Basestations
RF Instrumentation
Microwave Data Links
VHF/UHF 2-Way Radios
, LT, LTC and LTM are registered trademarks of Linear Technology Corporation.
All other trademarks are the property of their respective owners.
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TYPICAL APPLICATIO
Low Cost 900MHz Downconverting Mixer
2.7V TO 5.3V
LOIN
1µF
760MHz
IFOUT and IM3 Levels
vs RF Input Power
10
0
100pF
15nH
1
4.7pF
EN
2
3
RFIN
900MHz 100pF
6.8nH
LO+
EN
VCC
IN+
U1
LT5560
8
7
6.8nH
IN–
PGND
9
270nH
4.7pF
OUT+
6
OUT –
5
4.7pF
4
15nH
LO–
270nH
IFOUT
33pF 140MHz
POWER LEVEL (dBm/Tone)
1nF
100pF
IFOUT
–10
–20
–30
–40
–50
–60
–70
IM3
TA = 25°C
VCC = 3V
ICC = 13.3mA
fLO = 760MHz
fIF = 140MHz
–80
–20 –18 –16 –14 –12 –10 –8 –6 –4 –2
RF INPUT POWER (dBm)
270nH
4.7pF
0
5560 TA02
5560 TA01
5560f
1
LT5560
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PACKAGE/ORDER I FOR ATIO
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W W
W
ABSOLUTE
AXI U RATI GS
(Note 1)
TOP VIEW
Supply Voltage .........................................................5.5V
Enable Voltage ................................ –0.3V to VCC + 0.3V
LO Input Power (Differential) .............................+10dBm
Input Signal Power (Differential) ........................+10dBm
IN+, IN – DC Currents ..............................................10mA
OUT+, OUT – DC Current .........................................10mA
TJMAX .................................................................... 125°C
Operating Temperature Range .................–40°C to 85°C
Storage Temperature Range...................–65°C to 125°C
LO– 1
EN 2
IN+ 3
IN–
9
4
8
LO+
7
VCC
6
OUT+
5
OUT –
DD PACKAGE
8-LEAD (3mm × 3mm) PLASTIC DFN
TJMAX = 125°C, θJA = 43°C/W
EXPOSED PAD (PIN 9) IS GND
MUST BE SOLDERED TO PCB
ORDER PART NUMBER
DD PART MARKING
LT5560EDD
LCBX
Order Options Tape and Reel: Add #TR
Lead Free: Add #PBF Lead Free Tape and Reel: Add #TRPBF
Lead Free Part Marking: http://www.linear.com/leadfree/
Consult LTC Marketing for parts specified with wider operating temperature ranges.
DC ELECTRICAL CHARACTERISTICS
VCC = 3V, EN = 3V, TA = 25°C, unless otherwise noted. Test circuit
shown in Figure 1. (Note 3)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
2.7
3
5.3
V
Power Supply Requirements (VCC)
Supply Voltage
Supply Current
VCC = 3V, R1 = 3Ω
10
12
mA
Shutdown Current
EN = 0.3V, VCC = 3V
0.1
10
µA
Enable (EN) Low = Off, High = On
EN Input High Voltage (On)
2
V
EN Input Low Voltage (Off)
Enable Pin Input Current
0.3
EN = 3V
EN = 0.3V
V
25
0.1
µA
µA
Turn On Time
2
µs
Turn Off Time
5
µs
AC ELECTRICAL CHARACTERISTICS
(Notes 2 and 3)
PARAMETER
CONDITIONS
MIN
TYP
MAX
UNITS
Signal Input Frequency Range (Note 4)
Requires External Matching
< 4000
MHz
LO Input Frequency Range (Note 4)
Requires External Matching
< 4000
MHz
Signal Output Frequency Range (Note 4)
Requires External Matching
< 4000
MHz
5560f
2
LT5560
AC ELECTRICAL CHARACTERISTICS
VCC = 3V, EN = 3V, TA = 25°C, PIN = –20dBm (–20dBm/tone for 2-tone
IIP3 tests, Δf = 1MHz), PLO = –2dBm, unless otherwise noted. Test circuits are shown in Figures 1, 2 and 3. (Notes 2 and 3)
PARAMETER
CONDITIONS
MIN
Signal Input Return Loss
Z = 50Ω, External Match
15
dB
LO Input Return Loss
Z = 50Ω, External Match
15
dB
Signal Output Return Loss
Z = 50Ω, External Match
15
dB
LO Input Power
TYP
MAX
–6 to 1
UNITS
dBm
Upconverting Mixer Configuration: VCC = 3V, EN = 3V, TA = 25°C, PIN = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), PLO =
–2dBm, unless otherwise noted. High side LO for 450MHz tests, low side LO for 900MHz and 1900MHz tests. Test circuits are shown in
Figures 1 and 3. (Notes 2, 3 and 5)
PARAMETER
CONDITIONS
Conversion Gain
fIN = 70MHz, fOUT = 450MHz
fIN = 140MHz, fOUT = 900MHz
fIN = 140MHz, fOUT = 1900MHz
Conversion Gain vs Temperature
TA = –40°C to 85°C, fOUT = 900MHz
Input 3rd Order Intercept
MIN
TYP
MAX
UNITS
2.7
2.4
1.2
dB
dB
dB
– 0.015
dB/°C
fIN = 70MHz, fOUT = 450MHz
fIN = 140MHz, fOUT = 900MHz
fIN = 140MHz, fOUT = 1900MHz
9.6
9.0
8.0
dBm
dBm
dBm
Input 2nd Order Intercept
fIN = 70MHz, fOUT = 450MHz
fIN = 140MHz, fOUT = 900MHz
fIN = 140MHz, fOUT = 1900MHz
46
47
30
dBm
dBm
dBm
Single Sideband Noise Figure
fIN = 70MHz, fOUT = 450MHz
fIN = 140MHz, fOUT = 900MHz
fIN = 140MHz, fOUT = 1900MHz
8.8
9.3
10.3
dB
dB
dB
IN to LO Isolation (with LO Applied)
fIN = 70MHz, fOUT = 450MHz
fIN = 140MHz, fOUT = 900MHz
fIN = 140MHz, fOUT = 1900MHz
69
64
64
dB
dB
dB
LO to IN Leakage
fIN = 70MHz, fOUT = 450MHz
fIN = 140MHz, fOUT = 900MHz
fIN = 140MHz, fOUT = 1900MHz
–63
–54
–36
dBm
dBm
dBm
LO to OUT Leakage
fIN = 70MHz, fOUT = 450MHz
fIN = 140MHz, fOUT = 900MHz
fIN = 140MHz, fOUT = 1900MHz
–44
–41
–36
dBm
dBm
dBm
Input 1dB Compression Point
fIN = 70MHz, fOUT = 450MHz
fIN = 140MHz, fOUT = 900MHz
fIN = 140MHz, fOUT = 1900MHz
0.4
–2.8
–0.8
dBm
dBm
dBm
Downconverting Mixer Configuration: VCC = 3V, EN = 3V, TA = 25°C, PIN = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz),
PLO = –2dBm, unless otherwise noted. High side LO for 450MHz tests, low side LO for 900MHz and 1900MHz tests. Test circuits are
shown in Figures 2 and 3. (Notes 2, 3 and 5)
PARAMETER
CONDITIONS
Conversion Gain
fIN = 450MHz, fOUT = 70MHz
fIN = 900MHz, fOUT = 140MHz
fIN = 1900MHz, fOUT = 140MHz
Conversion Gain vs Temperature
TA = – 40°C to 85°C, fIN = 900MHz
Input 3rd Order Intercept
Single Sideband Noise Figure
MIN
TYP
2.7
2.6
2.3
MAX
UNITS
dB
dB
dB
– 0.015
dB/°C
fIN = 450MHz, fOUT = 70MHz
fIN = 900MHz, fOUT = 140MHz
fIN = 1900MHz, fOUT = 140MHz
10.1
9.7
5.6
dBm
dBm
dBm
fIN = 450MHz, fOUT = 70MHz
fIN = 900MHz, fOUT = 140MHz
fIN = 1900MHz, fOUT = 140MHz
10.5
10.1
10.8
dB
dB
dB
5560f
3
LT5560
AC ELECTRICAL CHARACTERISTICS
Downconverting Mixer Configuration: VCC = 3V, EN = 3V, TA = 25°C,
PIN = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), PLO = –2dBm, unless otherwise noted. High side LO for 450MHz tests,
low side LO for 900MHz and 1900MHz tests. Test circuits are shown in Figures 2 and 3. (Notes 2, 3 and 5)
PARAMETER
CONDITIONS
MIN
IN to LO Isolation (with LO Applied)
fIN = 450MHz, fOUT = 70MHz
fIN = 900MHz, fOUT = 140MHz
fIN = 1900MHz, fOUT = 140MHz
52
52
25
dB
dB
dB
LO to IN Leakage
fIN = 450MHz, fOUT = 70MHz
fIN = 900MHz, fOUT = 140MHz
fIN = 1900MHz, fOUT = 140MHz
–52
–57
–37
dBm
dBm
dBm
LO to OUT Leakage
fIN = 450MHz, fOUT = 70MHz
fIN = 900MHz, fOUT = 140MHz
fIN = 1900MHz, fOUT = 140MHz
–47
–63
–24
dBm
dBm
dBm
2RF – 2LO Output Spurious (Half IF)
Product (fIN = fLO + fOUT/2)
450MHz: fIN = 485MHz, fOUT = 70MHz
900MHz: fIN = 830MHz, fOUT = 140MHz
1900MHz: fIN = 1830MHz, fOUT = 140MHz
–68
–69
–47
dBc
dBc
dBc
3RF – 3LO Output Spurious (1/3 IF)
Product (fIN = fLO + fOUT/3)
450MHz: fIN = 496.7MHz, fOUT = 69.9MHz
900MHz: fIN = 806.7MHz, fOUT = 140.1MHz
1900MHz: fIN = 1806.7MHz, fOUT = 140.1MHz
–79
–76
–62
dBc
dBc
dBc
Input 1dB Compression Point
fIN = 450MHz, fOUT = 70MHz
fIN = 900MHz, fOUT = 140MHz
fIN = 1900MHz, fOUT = 140MHz
–0.8
0
–2.2
dBm
dBm
dBm
Note 1: Stresses beyond those listed under Absolute Maximum Ratings
may cause permanent damage to the device. Exposure to any Absolute
Maximum Rating condition for extended periods may affect device
reliability and lifetime.
Note 2: Each set of frequency conditions requires an appropriate test board.
Note 3: Specifications over the –40°C to +85°C temperature range are
assured by design, characterization and correlation with statistical process
controls.
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Supply Current
vs Supply Voltage
UNITS
(Test Circuit Shown in Figure 1)
Shutdown Current
vs Supply Voltage
1.0
25°C
85°C
–40°C
25°C
85°C
–40°C
0.8
CURRENT (µA)
11
CURRENT (mA)
MAX
Note 4: Operation over a wider frequency range is possible with reduced
performance. Consult the factory for information and assistance.
Note 5: SSB Noise Figure measurements are performed with a smallsignal noise source and bandpass filter on the RF input (downmixer) or
output (upmixer), and no other RF input signal applied.
TYPICAL DC PERFOR A CE CHARACTERISTICS
12
TYP
10
0.6
0.4
9
0.2
8
0.0
2.5
3
3.5
4
4.5
VOLTAGE (V)
5
5.5
5560 G01
2.5
3
3.5
4
4.5
VOLTAGE (V)
5
5.5
5560 G02
5560f
4
LT5560
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TYPICAL AC PERFOR A CE CHARACTERISTICS
900MHz Upconverting Mixer Application:
VCC = 3V, ICC = 10mA, EN = 3V, TA = 25°C, fIN = 140MHz, PIN = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), fLO = 760MHz,
PLO = –2dBm, output measured at 900MHz, unless otherwise noted. (Test circuit shown in Figure 1)
Conversion Gain, IIP3 and SSB NF
vs RF Output Frequency
15
10
14
IIP3
10
8
11
6
10
SSB NF
9
5
4
8
GAIN
3
7
2
6
1
5
0
850
870
890
910
930
RF OUTPUT FREQUENCY (MHz)
GAIN (dB), IIP3 (dBm)
12
NOISE FIGURE (dB)
7
17
IIP3
15
25°C
85°C
–40°C
6
4
GAIN
2
4
950
–2
–10
–8
0
–6
–4
–2
LO INPUT POWER (dBm)
7
–10
2
GAIN (dB), IIP3 (dBm)
10
LO-OUT
LO-IN
0
25°C
85°C
–40°C
IIP3
OUTPUT POWER (dBm/Tone)
–10
–30
–6
–4
–2
LO INPUT POWER (dBm)
0
9
8
7
6
5
4
GAIN
3
2
–60
2
RFOUT, IM3 and IM2 vs
IF Input Power (Two Input Tones)
12
–20
–8
5560 G05
Conversion Gain and IIP3
vs Supply Voltage
11
LEAKAGE (dBm)
11
10
5560 G04
0
RFOUT
–20
IM3
25°C
85°C
–40°C
–40
IM2
–60
–80
1
0
2.5
–70
700 720 740 760 780 800 820 840 860
LO FREQUENCY (MHz)
3
4.5
4
3.5
VOLTAGE (V)
5
–100
–20
5.5
–10
–15
–5
IF INPUT POWER (dBm)
0
5560 G07
5560 G06
Gain Distribution at 900MHz
5560 G08
SSB Noise Figure Distribution
at 900MHz
IIP3 Distribution at 900MHz
60
50
13
12
8
LO-IN and LO-OUT Leakage
vs LO Frequency
–50
14
9
0
5560 G03
–40
25°C
85°C
–40°C
16
13
25°C
85°C
–40°C
8
SSB Noise Figure
vs LO Input Power
NOISE FIGURE (dB)
11
9
GAIN (dB), IIP3 (dBm)
Conversion Gain and IIP3
vs LO Input Power
45
–45°C
+25°C
+90°C
60
–45°C
+25°C
+90°C
40
–45°C
+25°C
+90°C
50
40
30
20
DISTRIBUTION (%)
DISTRIBUTION (%)
DISTRIBUTION (%)
35
30
25
20
15
40
30
20
10
10
10
5
0
1.7 1.9 2.1 2.3 2.5 2.7 2.9 3.1 3.3 3.5
GAIN (dB)
5560 G09
0
0
7.8
8.2
8.6
9.0
9.4
IIP3 (dBm)
9.8
10.2
5560 G10
7.6
8.0
8.4 8.8 9.2 9.5
SSB NOISE FIGURE (dB)
10.0 10.4
5560 G11
5560f
5
LT5560
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TYPICAL AC PERFOR A CE CHARACTERISTICS
450MHz Upconverting Mixer Application:
VCC = 3V, ICC = 10mA, EN = 3V, TA = 25°C, fIN = 70MHz, PIN = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), fLO = 520MHz,
PLO = –2dBm, output measured at 450MHz, unless otherwise noted. (Test circuit shown in Figure 3)
Conversion Gain and IIP3
vs RF Output Frequency
14
IIP3
10
12
25°C
85°C
–40°C
8
7
NOISE FIGURE (dB)
6
5
GAIN
4
3
RFOUT
–10
11
10
9
8
7
–20
IM3
25°C
85°C
–40°C
–30
–40
IM2
–50
–60
–70
2
6
1
5
–80
0
350
4
350
–90
–20
400
450
500
RF OUTPUT FREQUENCY (MHz)
550
5560 G12
Conversion Gain and IIP3
vs LO Input Power
10
25°C
85°C
–40°C
16
15
IIP3
14
8
6
4
550
GAIN
0
5560 G14
LO-IN and LO-OUT Leakage
vs LO Frequency
0
25°C
85°C
–40°C
–10
–20
13
12
11
10
9
–30
–40
LO-OUT
–50
8
2
–60
7
0
–10
–10
–15
–5
IF INPUT POWER (dBm)
5560 G13
SSB Noise Figure
vs LO Input Power
NOISE FIGURE (dB)
12
400
450
500
RF OUTPUT FREQUENCY (MHz)
LEAKAGE (dBm)
GAIN (dB), IIP3 (dBm)
9
0
25°C
85°C
–40°C
13
OUTPUT POWER (dBm/Tone)
11
GAIN (dB), IIP3 (dBm)
RFOUT, IM3 and IM2 vs IF Input
Power (Two Input Tones)
SSB Noise Figure
vs RF Output Frequency
–8
–6
–4
–2
LO INPUT POWER (dBm)
0
6
–10
2
5560 G15
–8
–2
–4
–6
LO INPUT POWER (dBm)
0
–70
350
2
5560 G16
LO-IN
400
450
500
550
LO FREQUENCY (MHz)
600
650
5560 G17
1900MHz Upconverting Mixer Application: VCC = 3V, ICC = 10mA, EN = 3V, TA = 25°C, fIN = 140MHz, PIN = –20dBm (–20dBm/tone for
2-tone IIP3 tests, Δf = 1MHz), fLO = 1760MHz, PLO = –2dBm, output measured at 1900MHz, unless otherwise noted. (Test circuit shown
in Figure 1)
Conversion Gain and IIP3
SSB Noise Figure
RFOUT, IM3 and IM2 vs IF Input
Power (Two Input Tones)
vs RF Output Frequency
vs RF Output Frequency
14
10
13
IIP3
12
8
NOISE FIGURE (dB)
GAIN (dB), IIP3 (dBm)
9
7
6
5
4
3
25°C
85°C
–40°C
GAIN
2
RFOUT
–10
11
10
9
8
7
6
1
1950
1900
1850
RF OUTPUT FREQUENCY (MHz)
2000
5560 018
4
1800
–20
–30
25°C
85°C
–40°C
IM3
–40
–50
IM2
–60
–70
5
0
–1
1800
0
25°C
85°C
–40°C
OUTPUT POWER (dBm/Tone)
11
1850
1900
1950
RF OUTPUT FREQUENCY (MHz)
2000
5560 G19
–80
–20
–10
–15
–5
IF INPUT POWER (dBm)
0
5560 G20
5560f
6
LT5560
U W
TYPICAL AC PERFOR A CE CHARACTERISTICS
1900MHz Upconverting Mixer Application:
VCC = 3V, ICC = 10mA, EN = 3V, TA = 25°C, fIN = 140MHz, PIN = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), fLO = 1760MHz,
PLO = –2dBm, output measured at 1900MHz, unless otherwise noted. (Test circuit shown in Figure 1)
Conversion Gain and IIP3
vs LO Input Power
SSB Noise Figure
vs LO Input Power
10
19
4
GAIN
2
0
–10
15
LEAKAGE (dBm)
25°C
85°C
–40°C
NOISE FIGURE (dB)
GAIN (dB), IIP3 (dBm)
17
6
0
25°C
85°C
–40°C
IIP3
8
LO-IN and LO-OUT Leakage
vs LO Frequency
13
11
–20
LO-OUT
–30
LO-IN
–40
9
–2
–4
–10
–8
–2
–4
–6
LO INPUT POWER (dBm)
0
7
–10
2
–8
5560 G21
–6
–4
–2
LO INPUT POWER (dBm)
0
–50
1660
2
5560 G22
1760
1710
1810
LO FREQUENCY (MHz)
1860
5560 G23
900MHz Downconverting Mixer Application: VCC = 3V, ICC = 10mA, EN = 3V, TA = 25°C, fIN = 900MHz, PIN = –20dBm (–20dBm/tone for
2-tone IIP3 tests, Δf = 1MHz), fLO = 760MHz, PLO = –2dBm, output measured at 140MHz, unless otherwise noted. (Test circuit shown in
Figure 2)
Conversion Gain, IIP3 and SSB NF
vs RF Input Frequency
IIP3
25°C
85°C
–40°C
9
GAIN
3
7
1
5
–1
700
900
1000
1100
800
RF INPUT FREQUENCY (MHz)
8
2
3
1200
–2
–10
5560 G24
–8
–2
–4
–6
LO INPUT POWER (dBm)
–10
–10
OUTPUT POWER (dBm)
–20
–30
–40
LO-IN
–60
600
700
900 1000
800
LO FREQUENCY (MHz)
1100
5560 G27
2
5560 G26
TA = 25°C
fLO = 760MHz
–60 fIF = 140MHz
3RF – 3LO
fRF = 806.7MHz
–40
–50
–60
2RF – 2LO
–70 fRF = 830MHz
–100
–20
0
–50
–20
–90
–6
–4
–2
LO INPUT POWER (dBm)
2 × 2 and 3 × 3 Spurs vs
LO Input Power (Single Input Tone)
IFOUT
fRF = 900MHz
–30
–80
LO-OUT
–8
5560 G25
IFOUT, 2 × 2 and 3 × 3 Spurs vs
RF Input Power (Single Input Tone)
0
–70
11
7
– 10
2
0
10
–50
13
9
0
0
LEAKAGE (dBm)
GAIN
4
LO-IN and LO-OUT Leakage
vs LO Frequency
–80
500
25°C
85°C
–40°C
6
OUTPUT POWER (dBm)
5
11
15
GAIN (dB), IIP3 (dBm)
SSB NF
25°C
85°C
–40°C
IIP3
10
13
7
17
12
NOISE FIGURE (dB)
GAIN (dB), IIP3 (dBm)
9
15
SSB Noise Figure
vs LO Input Power
NOISE FIGURE (dB)
11
Conversion Gain and IIP3
vs LO Input Power
TA = 25°C
fLO = 760MHz
fIF = 140MHz
–15
–10
–5
RF INPUT POWER (dBm)
–70
–80
–90
–100
0
5560 G28
2RF – 2LO
fRF = 830MHz
3RF – 3LO
fRF = 806.7MHz
–110
–10
–8
–6
–4
–2
LO INPUT POWER (dBm)
0
2
5560 G29
5560f
7
LT5560
U W
TYPICAL AC PERFOR A CE CHARACTERISTICS
900MHz Downconverting Mixer Application:
VCC = 3V, ICC = 10mA, EN = 3V, TA = 25°C, fIN = 900MHz, PIN = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz), fLO = 760MHz,
PLO = –2dBm, output measured at 140MHz, unless otherwise noted. (Test circuit shown in Figure 2)
Conversion Gain and IIP3
vs Supply Voltage
IFOUT and IM3 vs RF Input Power
(Two Input Tones)
12
10
11
IIP3
OUTPUT POWER (dBm/Tone)
GAIN (dB), IIP3 (dBm)
9
8
7
6
25°C
85°C
–40°C
5
GAIN
4
3
2
–10
IFOUT
–20
–30
IM3
–40
–50
–60
–70
–80
1
0
2.5
25°C
85°C
–40°C
0
10
3
4.5
4
3.5
VOLTAGE (V)
5
–90
–20 –18 –16 –14 –12 –10 –8 –6 –4 –2 0
RF INPUT POWER (dBm)
5560 G31
5.5
5560 G30
450MHz Downconverting Mixer Application: VCC = 3V, ICC = 10mA, EN = 3V, TA = 25°C, fIN = 450MHz, PIN = –20dBm (–20dBm/tone for
2-tone IIP3 tests, Δf = 1MHz), fLO = 520MHz, PLO = –2dBm, output measured at 70MHz, unless otherwise noted. (Test circuit shown in
Figure 3)
Conversion Gain and IIP3
SSB Noise Figure
Conversion Gain, IIP3 and SSB NF
vs LO Input Power
vs LO Input Power
vs RF Input Frequency
17
13
12
17
11
25°C
85°C
–40°C
IIP3
IIP3
15
10
13
8
9
GAIN
3
7
1
5
–1
350
400
450
500
RF INPUT FREQUENCY (MHz)
GAIN
4
2
–2
–10
3
550
5560 G32
–8
–2
–4
–6
LO INPUT POWER (dBm)
OUTPUT POWER (dBm)
–10
–20
–30
–50
LO-IN
470
520
570
LO FREQUENCY (MHz)
620
5560 G35
–110
–20
0
2
5560 G34
–50
TA = 25°C
fLO = 520MHz
–60 fIF = 70MHz
3RF – 3LO
fRF = 496.7MHz
–50
–90
–60
–6
–4
–2
LO INPUT POWER (dBm)
2 × 2 and 3 × 3 Spurs vs
LO Input Power (Single Input Tone)
IFOUT
fRF = 450MHz
–30
–70
–8
5560 G33
IFOUT, 2 × 2 and 3 × 3 Spurs vs
RF Input Power (Single Input Tone)
–10
LO-OUT
11
7
– 10
2
0
10
–40
13
9
0
0
LEAKAGE (dBm)
25°C
85°C
–40°C
6
LO-IN and LO-OUT Leakage
vs LO Frequency
–70
420
NOISE FIGURE (dB)
5
11
OUTPUT POWER (dBm)
GAIN (dB), IIP3 (dBm)
SSB NF
NOISE FIGURE (dB)
7
GAIN (dB), IIP3 (dBm)
15
25°C
85°C
–40°C
9
2RF – 2LO
fRF = 485MHz
TA = 25°C
fLO = 520MHz
fIF = 70MHz
–15
–10
–5
RF INPUT POWER (dBm)
–70
–80
–90
2RF – 2LO
fRF = 485MHz
3RF – 3LO
fRF = 496.7MHz
–100
0
5560 G36
–110
–10
–8
–6
–4
–2
LO INPUT POWER (dBm)
0
2
5560 G37
5560f
8
LT5560
U W
TYPICAL AC PERFOR A CE CHARACTERISTICS
1900MHz Downconverting Mixer Application:
VCC = 3V, ICC = 10mA, EN = 3V, TA = 25°C, fIN = 1900MHz, PIN = –20dBm (–20dBm/tone for 2-tone IIP3 tests, Δf = 1MHz),
fLO = 1760MHz, PLO = –2dBm, output measured at 140MHz, unless otherwise noted. (Test circuit shown in Figure 2)
Conversion Gain, IIP3 and SSB NF
vs RF Input Frequency
Conversion Gain and IIP3
vs LO Input Power
12
10
8
GAIN (dB)
6
GAIN
2
0
1700 1750
1800 1850 1900 1950
INPUT FREQUENCY (MHz)
4
0
0
–2
–8
5560 G38
–6
–4
–2
LO INPUT POWER (dBm)
0
2
–4
5560 G39
LO-IN and LO-OUT Leakage
vs LO Frequency
17
0
15
–10
LEAKAGE (dBm)
NOISE FIGURE (dB)
2
GAIN
–2
–10
2000
4
2
SSB Noise Figure
vs LO Input Power
13
11
–20
LO-OUT
–30
LO-IN
9
7
– 10
–40
25°C
85°C
–40°C
–8
–6
–4
–2
LO INPUT POWER (dBm)
0
–50
1560
2
TA = 25°C
fLO = 1760MHz
–50 fIF = 140MHz
OUTPUT POWER (dBm)
2RF – 2LO
fRF = 1830MHz
–70
3RF – 3LO
fRF = 1806.7MHz
–90
–20
1860
5560 G41
–40
IFOUT
fRF = 1900MHz
–30
–50
1660 1710 1760 1810
LO FREQUENCY (MHz)
2 × 2 and 3 × 3 Spurs vs
LO Input Power (Single Input Tone)
10
–10
1610
5560 G40
IFOUT, 2 × 2 and 3 × 3 Spurs vs
RF Input Power (Single Input Tone)
OUTPUT POWER (dBm)
25°C
85°C
–40°C
6
IIP3
4
6
8
25°C
85°C
–40°C
IIP3 (dBm)
GAIN, NF (dB), IIP3 (dBm)
10
8
IIP3
SSB NF
TA = 25°C
fLO = 1760MHz
fIF = 140MHz
–15
–10
–5
RF INPUT POWER (dBm)
2RF – 2LO
fRF = 1830MHz
–60
–70
3RF – 3LO
fRF = 1806.7MHz
–80
–90
0
5560 G42
–100
–10
–8
–6
–4
–2
LO INPUT POWER (dBm)
0
2
5560 G43
5560f
9
LT5560
U
U
U
PI FU CTIO S
LO –, LO+ (Pins 1, 8): Differential Inputs for the Local
Oscillator Signal. The LO input impedance is approximately 180Ω, thus external impedance matching is
required. The LO pins are internally biased to approximately 1V below VCC; therefore, DC blocking capacitors
are required. The LT5560 is characterized and production
tested with a single-ended LO drive, though a differential
LO drive can be used.
Each pin requires a DC current path to ground. Resistance
to ground will cause a decrease in the mixer current. With
0Ω resistance, approximately 6mA of DC current flows
out of each pin. For lowest LO leakage to the output, the
DC resistance from each pin to ground should be equal.
An impedance transformation is required to match the
differential input to the desired source impedance.
EN (Pin 2): Enable Pin. An applied voltage above 2V will
activate the IC. For VEN below 0.3V, the IC will be shut
down. If the enable function is not required, then this pin
should be connected to VCC. The typical enable pin input
current is 25µA for EN = 3V. The enable pin should not be
allowed to float because the mixer may not turn on reliably.
Note that at no time should the EN pin voltage be allowed
to exceed VCC by more than 0.3V.
VCC (Pin 7): Power Supply Pin for the Bias Circuits.
Typical current consumption is 1.5mA. This pin should
be externally bypassed with a 1nF chip capacitor.
IN+, IN– (Pins 3, 4): Differential Inputs. These pins should be
driven with a differential signal for optimum performance.
OUT –, OUT+ (Pins 5, 6): Differential Outputs. An impedance transformation may be required to match the outputs.
These pins require a DC current path to VCC .
Exposed Pad (Pin 9): PGND. Circuit Ground Return for
the Entire IC. This must be soldered to the printed circuit
board ground plane.
5560f
10
LT5560
W
BLOCK DIAGRA
LO–
1
PGND
9
LO+
8
INPUT BUFFER
AMPLIFIER
IN+ 3
6 OUT +
IN– 4
5 OUT –
DOUBLEBALANCED
MIXER
BIAS
2
7
EN
VCC
5560 BD
5560f
11
LT5560
TEST CIRCUITS
LOIN
C3
C7
L5
C4
C5
VCC
C9
1
EN
IN
T1
6
L1
1
2
4
3
L2
LO+
VCC
EN
8
7
LT5560
3
2
C1
LO–
4
IN+
IN–
OUT
+
OUT –
PGND
C8
C6
6
5
L4
OUT
T2
L3
3
1
2
4
5
C10
R1
5560 F01
Component Values for fOUT = 900MHz, fIN = 140MHz and fLO = 760MHz
REF DES
VALUE
SIZE
PART NUMBER
REF DES
VALUE
SIZE
PART NUMBER
C1
22pF
0402
AVX 04025A220JAT
L1, L2
18nH
1005
Toko LL1005-FH18NJ
C3, C5
100pF
0402
AVX 04025A101JAT
L3, L4
27nH
1005
Toko LL1005-FH27NJ
C4
1pF
0402
AVX 04025A1R0BAT
L5
12nH
1005
Toko LL1005-FH12NJ
C6, C9
1nF
0402
AVX 04023C102JAT
R1
3Ω
0402
C8
1µF
0603
Taiyo Yuden LMK107BJ105MA
T1
1:1
Coilcraft WBC1-1TL
C10
2.2pF
0402
AVX 04025A2R2BAT
T2
4:1
TDK HHM1515B2
Note: C7 not used.
Component Values for fOUT = 1900MHz, fIN = 140MHz and fLO = 1760MHz
REF DES
VALUE
SIZE
PART NUMBER
REF DES
VALUE
SIZE
PART NUMBER
C1
22pF
0402
AVX 04025A220JAT
L1, L2
18nH
1005
Toko LL1005-FH18NJ
C3
100pF
0402
AVX 04025A101JAT
L3, L4
3.9nH
1005
Toko LL1005-FH3N9S
C7
Toko LL1005-FH5N6S
1.5pF
0402
AVX 04025A1R5BAT
L5
5.6nH
1005
C6, C9
1nF
0402
AVX 04023C102JAT
R1
3Ω
0402
C8
1µF
0603
Taiyo Yuden LMK107BJ105MA
T1
1:1
Coilcraft WBC1-1TL
C10
1pF
0402
AVX 04025A1R0BAT
T2
1:1
TDK HHM1525
Note: C4 and C5 are not used.
Figure 1. Test Schematic for 900MHz and 1900MHz Upconverting
Mixer Applications with 140MHz Input
5560f
12
LT5560
TEST CIRCUITS
LOIN
C3
C7
L5
C4
C5
VCC
1
EN
IN
T1
1
L1
4
2
5
C1
L2
LO+
EN
VCC
IN+
OUT+
7
IN–
OUT –
PGND
5
L4
OUT
T2
L3
6
C2
4
C8
C6
8
LT5560
3
2
3
LO–
3
4
2
1
6
R1
5560 F02
Component Values for fIN = 900MHz, fOUT = 140MHz and fLO = 760MHz
REF DES
VALUE
SIZE
PART NUMBER
REF DES
VALUE
SIZE
PART NUMBER
C1
2.2pF
0402
AVX 04025A2R2BAT
L1, L2
0Ω
1005
0Ω Resistor
C2
1.2pF
0402
AVX 04025A1R2BAT
L3, L4
220nH
1608
Toko LL1608-FSR22J
C3, C5
Toko LL1005-FH12NJ
100pF
0402
AVX 04025A101JAT
L5
12nH
0402
C4
1pF
0402
AVX 04025A1R0BAT
R1
3Ω
0402
C6
1nF
0402
AVX 04023C102JAT
T1
1:1
TDK HHM1522B1
C8
1µF
0603
Taiyo Yuden LMK107BJ105MA
T2
4:1
M/A-COM MABAES0061
Note: C7 not used.
Component Values for fIN = 1900MHz, fOUT = 140MHz and fLO = 1760MHz
REF DES
VALUE
SIZE
PART NUMBER
REF DES
VALUE
SIZE
PART NUMBER
C1
1.0pF
0402
AVX 04025A1R0BAT
L1, L2
0Ω
1005
0Ω Resistor
C2
1.2pF
0402
AVX 04025A1R2BAT
L3, L4
220nH
1608
Toko LL1608-FSR22J
C3
100pF
C7
1.5pF
0402
AVX 04025A101JAT
L5
5.6nH
1005
Toko LL1005-FH5N6S
0402
AVX 04025A1R5BAT
R1
3Ω
0402
C6
1nF
0402
AVX 04023C102JAT
T1
2:1
TDK HHM1526
C8
1µF
0603
Taiyo Yuden LMK107BJ105MA
T2
4:1
M/A-COM MABAES0061
Note: C4 and C5 are not used.
Figure 2. Test Schematic for 900MHz and 1900MHz Downconverting
Mixer Applications with 140MHz Input
5560f
13
LT5560
TEST CIRCUITS
LOIN
C3
L5
C4
C5
VCC
EN
IN
C11
T1
6
L1
1
2
4
3
L2
LO+
EN
VCC
4
7
IN+
OUT+
6
IN–
OUT –
5
PGND
C8
C6
8
LT5560
3
2
C1
LO–
L4
OUT
T2
L3
3
4
2
1
6
C10
R1
5560 F03
Upconverting Mixer Component Values for fIN = 70MHz, fOUT = 450MHz and fLO = 520MHz
REF DES
VALUE
SIZE
PART NUMBER
REF DES
VALUE
SIZE
PART NUMBER
C1
39pF
0402
AVX 04025390JAT
L1, L2
33nH
1005
Toko LL1005-FH33NJ
C3, C5, C6
1nF
0402
AVX 04023C102JAT
L3, L4
68nH
1608
Toko LL1608-FS68NJ
Toko LL1005-FH22NJ
C4
1.5pF
0402
AVX 04025A1R5BAT
L5
22nH
1005
C8
1µF
0603
Taiyo Yuden LMK107BJ105MA
R1
3Ω
0402
C10
1.5pF
0402
AVX 04025A1R5BAT
T1
1:1
Coilcraft WBC1-1TL
T2
4:1
M/A-COM MABAES0061
Note: C11 is not used.
Downconverting Mixer Component Values for fIN = 450MHz, fOUT = 70MHz and fLO = 520MHz
REF DES
VALUE
SIZE
PART NUMBER
REF DES
1nF
0402
AVX 04023C102JAT
L3, L4
1.5pF
0402
AVX 04025A1R5BAT
C8
1µF
0603
C11
5.6pF
0603
0Ω
0402
0Ω Resistor
C3, C5, C6
C4
L1, L2
VALUE
SIZE
PART NUMBER
0Ω
0402
0Ω Resistor
L5
22nH
0402
Toko LL1005-FH22NJ
Taiyo Yuden LMK107BJ105MA
R1
3Ω
0402
AVX 06035A5R6BAT
T1
1:1
Coilcraft WBC1-1TL
T2
16:1
Coilcraft WBC16-1TL
Note: C1 and C10 not used.
Figure 3. Test Schematic for 450MHz Upconverting
Mixer and Downconverting Mixer Applications
5560f
14
LT5560
U
W
U
U
APPLICATIO S I FOR ATIO
The LT5560 consists of a double-balanced mixer, a common-base input buffer amplifier, and bias/enable circuits.
The IC has been designed for frequency conversion applications up to 4GHz, though operation over a wider frequency
range may be possible with reduced performance. For best
performance, the input and output should be connected
differentially. The LO input can be driven by a single-ended
source with either low side or high side LO operation. The
LT5560 is characterized and production tested using a
single-ended LO drive.
provided through the center-tap of an input transformer,
as shown, or through matching inductors or chokes connected from pins 3 and 4 to ground.
LT5560
INPUT
Table 1. LT5560 Demo Board Descriptions
DEMO
BOARD
NUMBER
INPUT
FREQ.
(MHz)
OUTPUT
FREQ.
(MHz)
LO
FREQ.
(MHz)
Upconverting,
Cellular Band
DC963B
50-190
850-940
530-930
Downconverting
Cellular Band
DC991A
710-1300
110-170
530-930
Downconverting,
VHF Band
DC1027A
MIXER
DESCRIPTION
115-295
3-60
180-310
Note: Consult factory for demo boards for UMTS, WLAN and other bands.
Signal Input Port
3
C1
L2
4
IN –
The quiescent DC current of the LT5560 can be adjusted
from less than 4mA to approximately 13.5mA through
the use of an external resistor. This functionality gives the
user the ability to make application dependent trade-offs
between IIP3 performance and DC current.
Three demo boards, as described in Table 1, are available
depending on the desired application. The listed input
and output frequency ranges are based on measured
12dB return loss bandwidths and the LO port frequency
ranges are based on 10dB return loss bandwidths. The
general circuit topologies are shown in Figures 1, 2 and
3 for DC963B, DC991A and DC1027A, respectively. The
board layouts are shown in Figures 23, 24 and 25. The
low frequency board, DC1027A, can be reconfigured for
upconverting applications.
IN+
L1
T1
VBIAS
R1
5560 F04
Figure 4. Input Port with Lowpass
External Matching Topology
The lowpass impedance matching topology shown may
be used to transform the differential input impedance
at pins 3 and 4 to match that of the signal source. The
differential input impedances for several frequencies are
listed in Table 2.
Table 2. Input Signal Port Differential Impedance
FREQUENCY
(MHz)
INPUT
IMPEDANCE
(Ω)
70
REFLECTION COEFFICIENT (ZO = 50Ω)
MAG
ANGLE (DEG.)
28.5 + j0.8
0.274
177
140
28.5 + j1.6
0.274
174
240
28.6 + j2.7
0.275
171
360
28.6 + j4.0
0.276
167
450
28.6 + j4.9
0.278
163
750
28.8 + j8.2
0.287
153
900
28.8 + j9.8
0.294
148
1500
29.1 + j16.3
0.328
138
1900
29.4 + j20.8
0.357
120
2150
29.6 + j23.6
0.376
114
2450
29.9 + j27.0
0.399
107
3600
31.7 + j42.1
0.499
86.2
Figure 4 shows a simplified schematic of the differential
input signal port and an example topology for the external
impedance matching circuit. Pins 3 and 4 each source
up to 6mA of DC current. This current can be reduced by
the addition of resistor R1 (adjustable mixer current is
discussed in a later section). The DC ground path can be
5560f
15
LT5560
U
W
U
U
APPLICATIO S I FOR ATIO
The following example demonstrates the design of a
lowpass impedance transformation network for a signal
input at 900MHz.
The simplified input circuit is shown in Figure 5. For this
example, the input transformer has a 1:1 impedance ratio,
so RS = 50Ω. From Table 2, at 900MHz, the differential
input impedance is: RL + jXINT = 28.8 + j9.8Ω. The internal
reactance will be used as part of the impedance matching
network. The matching circuit consists of additional external series inductance (L1 and L2) and a capacitance (C1)
in parallel with the 50Ω source impedance. The external
capacitance and inductance are calculated below.
First, calculate the impedance transformation ratio (n)
and the network Q:
R
50
n= S =
= 1 . 74
RL 28 . 8
The internal inductance has been accounted for by subtracting the internal reactance (XINT) from the total reactance
(XL). Small inductance values may be realized using highimpedance printed transmission lines instead of lumped
inductors. The equations above provide good starting
values, though the values may need to be optimized to
account for layout and component parasitics.
LT5560
L1
XEXT/2
XINT/2
3
RS
50Ω
C1
RL
28.1Ω
L2
XEXT/2
XINT/2
4
5560 F05
Q=
(n − 1) = 0 . 858
Figure 5. Small Signal Circuit for the Input Port
Next, the capacitance and inductance can be calculated
as follows:
XC =
RS
= 58 . 3Ω
Q
C1 =
1
= 3 . 03pF
ω • XC
XL = RL • Q = 24.7Ω
XEXT = XL – XINT = 14.9Ω
L1 = L2 =
L EXT X EXT
=
= 1 . 32nH
2
2ω
5560f
16
LT5560
Table 3 lists actual component values used on the LT5560
evaluation boards for impedance matching at various
frequencies. The measured Input Return Loss vs Frequency performance is plotted for several of the cases
in Figure 6.
Table 3. Component Values for Input Matching
CASE
FREQ.
(MHz)
T1
C1
(pF)
L1, L2
(nH)
MATCH BW
(@12dB RL)
1
10
WBC1-1TL 1:1
220
180
6-18
2
70
WBC1-1TL 1:1
39
33
29-102
3
140
WBC1-1TL 1:1
22
18
50-190
4
240
WBC1-1TL 1:1
15
12
115-295
5
4501
WBC1-1TL 1:1
NA
0
390-560
6
900
HHM1522B1 1:1
2.2
0
710-1630
7
1900
HHM1526 2:1
1
0
1660-2500
8
2450
HHM1520A2 2:1
1
0
1640-2580
9
3600
HHM1583B1 2:1
0.5
0
3330-3840
LO Input Port
Figure 7 shows a simplified schematic of the LO input. The
LO input connections drive the bases of the mixer transistors, while a 200Ω resistor across the inputs provides the
impedance termination. The internal 1kΩ bias resistors are
in parallel with the input resistor resulting in a net input
DC resistance of approximately 180Ω. The pins are biased
by an internally generated voltage at approximately
1V below VCC; thus external DC blocking capacitors are
required. If desired, the LO inputs can be driven differentially. The required LO drive at the IC is 240mVRMS (typ)
which can come from a 50Ω source or a higher impedance
such as PECL.
LT5560
1k
C5
Note 1: Series 5.6pF capacitor is used at the input (see Figure 3).
–5
RETURN LOSS (dB)
8
1
2
3
4
1
9
C7
–10
200Ω
L5
7
5
1k
LO+
VCC
LOIN
50Ω C3
0
VBIAS
LO–
C4
5560 F07
6
–15
Figure 7. LO Input Schematic
–20
–25
–30
10
100
1000
FREQUENCY (MHz)
4000
5560 F06
Figure 6. Input Return Loss vs Frequency
for Different Matching Values
5560f
17
LT5560
U
U
W
U
APPLICATIO S I FOR ATIO
Table 4. Single-Ended LO Input Impedance (Parallel Equivalent)
FREQUENCY
(MHz)
INPUT
IMPEDANCE
(Ω)
REFLECTION COEFFICIENT (ZO = 50Ω)
MAG
ANGLE (DEG.)
150
161 || –j679
0.529
–9.3
520
142 || –j275
0.494
–23.3
760
130 || –j192
0.475
–33.5
1660
74 || –j98
0.347
–74.5
1760
69 || –j94
0.330
–80.1
2040
60 || –j89
0.308
–90.1
2210
51 || –j91
0.266
–104
3150
50 || –j103
0.235
–104
3340
33 || –j41
0.472
–138
Table 5. Component Values for LO Input Matching
CASE
FREQ.
(MHz)
C4
(pF)
L5
(nH)
C7
(pF)
C3, C5
(pF)
MATCH BW
(@12dB RL)
1
150
8.2
68
-
1000
120-180
2
250
4.7
47
-
1000
195-300
3
520
1.5
22
-
1000
390-605
4
760
1
12
-
100
590-890
5
1200
-
6.8
-
100
850-1430
1540-1890
6
1760
-
4.7
1
1001
7
2900
-
1
1
10
2690-3120
8
3150
-
0
-
10
2990-3480
Note 1: C5 is not used at 1760MHz
0
–5
4
RETURN LOSS (dB)
Reactive matching from the LO source to the LO input is
recommended to take advantage of the resulting voltage
gain. To assist in matching, Table 4 lists the single-ended
input impedances of the LO input port. Actual component values, for several LO frequencies, are listed in
Table 5. Figure 8 shows the typical return loss response
for each case.
6
8
–10
–15
1
2
3
–20
–25
–30
100
1000
FREQUENCY (MHz)
4000
5560 F08
Figure 8. Typical LO Input Return Loss vs
Frequency for Different Matching Values
5560f
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LT5560
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Signal Output Port
A simplified schematic of the output circuit is shown in
Figure 9. The output pins, OUT + and OUT –, are internally
connected to the collectors of the mixer transistors. These
pins must be biased at the supply voltage, which can be
applied through a transformer center-tap, impedance
matching inductors, RF chokes, or pull-up resistors. With
external resistor R1 = 3Ω (Figures 1 to 3), each OUT pin
draws about 4.5mA of supply current. For optimum performance, these differential outputs should be combined
externally through a transformer or balun.
An equivalent small-signal model for the output is shown
in Figure 10. The output impedance can be modeled as
a 1.2kΩ resistor in parallel with a 0.7pF capacitor. For
low frequency applications, the 0.7nH series bond-wire
inductances can be ignored.
The external components, C2, L3 and L4, form a lowpass
impedance transformation network to match the mixer
output impedance to the input impedance of transformer
T2. The values for these components can be estimated
LT5560
using the impedance parameters listed in Table 6 along
with similar equations as used for the input matching network. As an example, at an output frequency of 140MHz
and RL = 200Ω (using a 4:1 transformer for T2),
n=
R S 1082
=
= 5 . 41
RL
200
Q=
(n − 1) = 2 . 10
XC =
RS
= 515Ω
Q
C=
1
= 2 . 21pF
ω • XC
C2 = C – CINT = 1.51pF
XL = RL • Q = 420Ω
L3 = L 4 =
XL
= 239nH
2ω
LT5560
OUT+
L3
0.7nH
T2
OUT
6
6
OUT+
1.2k
RINT
1.2k
0.7pF
CINT
0.7pF
C2
OUT–
5560 F09
Figure 9. Output Port Schematic
C10
L4
0.7nH
5
5
VCC
VCC
OUT –
5560 F10
Figure 10. Output Port Small-Signal Model
with External Matching
5560f
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Table 6. Output Port Differential Impedance (Parallel Equivalent)
REFLECTION COEFFICIENT (ZO = 50Ω)
Table 7 lists actual component values used on the
LT5560 evaluation boards for impedance matching at
several frequencies. The measured output return loss
vs frequency performance is plotted for several of the
cases in Figure 11.
FREQUENCY
(MHz)
OUTPUT
IMPEDANCE
(Ω)
70
1098 || –j3185
140
1082 || –j1600
0.912
–3.6
240
1082 || –j974
0.912
–5.9
360
1093 || –j646
0.913
–8.9
450
1083 || –j522
0.913
–11.0
750
1037 || –j320
0.910
–17.8
1
900
946 || –j269
0.903
–21.1
2
1500
655 || –j162
0.870
–34.5
1900
592 || –j122
0.865
–44.6
2150
662 || –j108
0.883
–50.0
2450
612 || –j95.7
0.879
–55.4
3600
188 || –j53.1
0.756
–88.7
MAG
ANGLE (DEG.)
0.913
–1.8
Table 7. Component Values for Output Matching
C10
(pF)
MATCH
BW
(@12dB RL)
0
-
3-60
0
-1
3-60
1.5
220
-
110-170
MABAES0061
4:1
0.5
120
-
175-300
380
MABAES0061
4:1
-
68
-
290-490
6
450
MABAES0061
4:1
-
68
1.5
360-540
7
900
HHM1515B2 4:1
-
27
2.2
850-940
8
1900
HHM1525 1:1
-
3.9
1
1820-2000
FREQ.
CASE (MHz)
In cases where the calculated value of C2 is less than the
internal output capacitance, capacitor C10 can be used to
improve the impedance match.
T2
C2
(pF)
L3, L4
(nH)
10
WBC16-1TL 16:1
-
70
WBC16-1TL 16:1
-
3
140
MABAES0061
4:1
4
240
5
Note 1: A better 70MHz match can be realized by adding a shunt 180nH
inductor at the C10 location.
0
RETURN LOSS (dB)
–5
6
7
8
–10
–15
–20
3
4
–25
–30
0
500
1000
2000
1500
FREQUENCY (MHz)
2500
5560 F11
Figure 11. Output Return Loss vs Frequency
for Different Matching Values
5560f
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Figure 12 shows a simplified schematic of the EN pin
interface. The voltage necessary to turn on the LT5560 is
2V. To disable the chip, the enable voltage must be less
than 0.3V. If the EN pin is allowed to float, the chip will tend
to remain in its last operating state, thus it is not recommended that the enable function be used in this manner.
If the shutdown function is not required, then the EN pin
should be connected directly to VCC.
The voltage at the EN pin should never exceed the power
supply voltage (VCC) by more than 0.3V. If this should
occur, the supply current could be sourced through the
EN pin ESD diode, potentially damaging the IC.
VCC
LT5560
vs current of a 900MHz downconverting mixer is plotted
in Figure 15. In this example, a 1nF capacitor has been
placed in parallel to R1 for best noise figure.
14
TA = 25°C
VCC = 3V
13
12
SUPPLY CURRENT (mA)
Enable Interface
11
10
9
8
7
6
5
4
0
5
10
15
R1 (Ω)
20
25
30
5560 F13
Figure 13. Typical Supply Current vs R1 Value
14
EN
2
5560 F12
GAIN AND NF (dB), IIP3 (dBm)
12
60k
6
IIP3
4
GAIN
2
–2
Adjustable Supply Current
Figure 13 shows the supply current as a function of R1.
Note that the current will also be affected by parasitic
resistance in the matching components. Figure 14 illustrates the effect of supply current on Gain, IIP3 and
NF of a 900MHz upconverting mixer. The performance
SSB NF
8
TA = 25°C
fIF = 140MHz
VCC = 3V
PLO = –2dBm
fLO = 760MHz
0
Figure 12. Enable Input Circuit
4
6
8
12
10
SUPPLY CURRENT (mA)
14
5560 F14
Figure 14. 900MHz Upconverting Mixer Gain,
Noise Figure and IIP3 vs Supply Current
14
MEASURED WITH InF CAP ACROSS R1
12
GAIN AND NF (dB), IIP3 (dBm)
The LT5560 offers a direct trade-off between power supply current and linearity. This capability allows the user
to optimize the performance and power dissipation of
the mixer for a particular application. The supply current
can be adjusted by changing the value of resistor R1 at
the center-tap of the input balun. For downconversion
applications, a bypass capacitor in parallel with R1 may
be desired to minimize noise figure. The bypass capacitor
has a greater effect on noise figure at larger values of R1.
In upmixer configurations, adding a capacitor across R1
has little effect.
10
SSB NF
10
8
IIP3
6
4
GAIN
2
TA = 25°C
fIF = 140MHz
VCC = 3V
PLO = –2dBm
fLO = 760MHz
0
–2
4
6
8
12
10
SUPPLY CURRENT (mA)
14
5560 F15
Figure 15. 900MHz Downconverting Mixer Gain,
Noise Figure and IIP3 vs Supply Current
5560f
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14
11
Application Examples
IIP3
12
GAIN (dB), IIP3 (dBm)
9
SSB NF
7
fRF = 140MHz
fIF = 10MHz
fLO = 150MHz
5
IIP3
56
10
IIP2
54
52
8
50
fIF = 10MHz
fLO = fRF + fIF
GAIN
2
4
–8
0
–4
–2
–6
LO INPUT POWER (dBm)
2
5560 F17
Figure 17. LT5560 Performance in 140MHz
Downconverting Mixer Application
The LT5560 operation at higher frequencies is demonstrated in Figure 18, where the performance of a 3600MHz
downconverting mixer is shown. The conversion gain, IIP3
and DSB NF are plotted for an RF input frequency range
of 3300 to 3800MHz and an IF frequency of 450MHz. The
circuit is the same topology as shown in Figure 2.
48
46
210 230 250 270 290
OUTPUT FREQUENCY (MHz)
11
44
310
5560 F16
Figure 16. LT5560 Performance in 240MHz
Upconverting Mixer Application
The performance in a 140MHz downconverting mixer
application is plotted in Figure 17. In this case the gain,
IIP3 and NF are shown as a function of LO power with an
IF output frequency of 10MHz. The circuit topology for
this case is shown in Figure 3.
10
GAIN NF (dB), IIP3 (dBm)
0
170 190
IIP2 (dBm)
GAIN (dB), IIP3 (dBm)
12
4
1
–10
6
58
14
6
8
GAIN
3
Figure 16 demonstrates gain, IIP3 and IIP2 performance
versus RF Output Frequency for the LT5560 when used
as a 240MHz upconverting mixer. The input frequency
is 10MHz, with an LO frequency of 250MHz. The circuit
uses the topology shown in Figure 1.
10
NOISE FIGURE (dB)
The LT5560 may be used as an upconverting or
downconverting mixer in a wide variety of applications,
in addition to those identified in the datasheet. The following examples illustrate the versatility of the LT5560.
(The component values for each case can be found in
Tables 3, 5 and 7).
9
DSB NF
8
7
IIP3
6
5
4
3
GAIN
2
1
3300
3400
3600
3700
3500
RF INPUT FREQUENCY (MHz)
3800
5560 F18
Figure 18. LT5560 Performance as a
3600MHz Downconverting Mixer
5560f
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APPLICATIO S I FOR ATIO
Lumped Element Matching
The applications described so far have employed external
transformers or hybrid baluns to realize single-ended to
differential conversions and, in some cases, impedance
transformations. An alternate approach is to use lumpedelement baluns to realize the input or output matching
networks.
A lumped element balun topology is shown in Figure 19.
The desired component values can be estimated using
the equations below, where RA and RB are the terminating resistances on the unbalanced and balanced ports,
respectively. Variable fC is the desired center frequency.
(The resistances of the LT5560 input and output can be
found in Tables 2 and 6).
LO =
CO =
R A • RB
2 • π • fC
1
2 • π • fC • R A • RB
The computed values are approximate, as they don’t account for the effects of parasitics of the IC and external
components.
Inductor LDC is used to provide a DC path to ground or to
VCC depending on whether the circuit is used at the input
or output of the LT5560. In some cases, it is desirable to
make the value of LDC as large as practical to minimize
loading on the circuit; however, the value can also be optimized to tune the impedance match. The shunt inductor,
LO, provides the DC path for the other balanced port.
Capacitor CDC may be required for DC blocking but
can often be omitted if DC decoupling is not required.
LO
CO
CDC
RB
LO
RA
LDC
CO
5560 F19
Figure 19. Lumped Element Balun
In some applications, CDC is useful for optimizing the
impedance match.
The circuit shown on page 1 illustrates the use of lumped
element baluns. In this example, the LT5560 is used to
convert a 900MHz input signal down to 140MHz using a
760MHz LO signal.
For the 900MHz input, RA = 50Ω and RB = 28Ω (from
Table 2). The actual values used for CO and LO are 4.7pF
and 6.8nH, which agree very closely with the calculated
values of 4.7pF and 6.6nH. The 15nH shunt inductor, in
this case, has been used to optimize the impedance match,
while the 100pF cap provides DC decoupling.
At the 140MHz output, the values used for RA and RB
are 50Ω and 1080Ω (from Table 6), respectively, which
result in calculated values of CO = 4.9pF and LO = 265nH.
These values are very close to the actual values of 4.7pF
and 270nH. A shunt inductor (LDC) of 270nH is used here
and the 33pF blocking cap has been used to optimize the
impedance.
5560f
23
LT5560
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APPLICATIO S I FOR ATIO
Measured IFOUT and IM3 levels vs RF input power for the
mixer with lumped element baluns are shown on page 1.
Additional performance parameters vs RF input frequency
are plotted in Figure 20.
op-amp to demonstrate performance with an output frequency of 450KHz. Pull-up resistors R3 and R4 are used
at the open-collector IF outputs instead of large inductors.
The op-amp provides gain and converts the mixer differential outputs to single-ended. At low frequencies, the
LO port can be easily matched with a shunt resistor and
a DC blocking cap. This IF interface circuit can be used
for signals up to 1MHz.
13
GAIN AND NF (dB), IIP3 (dBm)
12
IIP3
11
10
SSB NF
Figure 21 shows an input match that uses a transformer
to present a differential signal to the mixer. A possible
alternative, shown in Figure 22, is to use a single-ended
drive on one input pin, with the other pin grounded. This
approach is more cost effective than the transformer,
however, some performance is sacrificed. Another option
is to use a lumped-element balun, which requires only one
more component than the single-ended impedance match,
but could provide better performance. Measured data for
the examples below are summarized in Table 8.
9
8
7
6
GAIN
5
4
800
1000
850
950
900
INPUT FREQUENCY (MHz)
5560 F20
Figure 20. Performance of 900MHz Downconverting
Mixer with Lumped Element Baluns
Table 8. Low-Frequency Performance
Low Frequency Applications
At low IF frequencies, where transformers can be impractical due to their large size and cost, alternate methods can
be used to achieve desired differential to single-ended
conversions. The examples in Figures 21 and 22 use an
LOIN
200.45MHz
R2
160Ω
fIN
(MHz)
fOUT
(MHz)
GC
(dB)
IIP3
(dBm)
DSB NF
(dB)
ICC
(mA)
200
0.45
9
3.8
11.6
14
90
0.45
6.8
3.3
22
18
C5
10nF
C3
10nF
1
VEN
RFIN
200MHz
T1
1:1
L1
12nH
C1
15pF
WBC4-6TL
2
R1
3Ω
L2
12nH
3
4
5V
LO–
8
LO+
EN
VCC
+
U1
LT5560
7
OUT+
IN–
5
OUT–
PGND
9
R3
200Ω
R4
200Ω
6
IN
R8
5.1kΩ
C6
1nF
C12
1µF
C11
1µF
R5
200Ω
C13
1µF
+
U2
LT6202
C8
1µF
R9
5.1kΩ
C14
1µF
IFOUT
R7
450kHz
51Ω
–
R6
200Ω
5560 F21
Figure 21. A 200MHz to 450KHz Downconverter with Active IF Interface
5560f
24
LT5560
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APPLICATIO S I FOR ATIO
LOIN
90.45MHz
R2
160Ω
C5
10nF
C3
10nF
1
VEN
RFIN
90MHz
2
L1
12nH
C1
56pF
3
L2
82nH
4
5V
LO–
LO+
EN
VCC
IN+
IN–
U1
LT5560
PGND
9
OUT+
OUT–
8
7
R8
5.1kΩ
C6
1nF
R3
200Ω
R4
200Ω
C11
1µF
6
C12
1µF
5
R5
200Ω
C13
1µF
+
U2
LT6202
C8
1µF
R9
5.1kΩ
C14
1µF
IFOUT
R7
450kHz
51Ω
–
R6
200Ω
5560 F22
Figure 22. 90MHz Downconverter with a Low Cost Discrete
Balun Input and a 450kHz Active IF Interface
Figure 23. Upconverting Mixer Evaluation Board (DC963B)—See Table 1
5560f
25
LT5560
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TYPICAL APPLICATIO S
Figure 24. Downconverting Mixer Evaluation Board (DC991A)—See Table 1
Figure 25. HF/VHF/UHF Upconverting or Downconverting
Mixer Evaluation Board (DC1027A)—See Table 1
5560f
26
LT5560
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PACKAGE DESCRIPTIO
DD8 Package
8-Lead Plastic DFN (3mm × 3mm)
(Reference LTC DWG # 05-08-1698)
0.675 ±0.05
3.5 ±0.05
1.65 ±0.05
(2 SIDES)
2.15 ±0.05
PACKAGE
OUTLINE
0.25 ± 0.05
0.50
BSC
2.38 ±0.05
(2 SIDES)
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONS
R = 0.115
TYP
5
3.00 ±0.10
(4 SIDES)
0.38 ± 0.10
8
1.65 ± 0.10
(2 SIDES)
PIN 1
TOP MARK
(NOTE 6)
(DD8) DFN 1203
0.200 REF
0.75 ±0.05
0.00 – 0.05
4
0.25 ± 0.05
1
0.50 BSC
2.38 ±0.10
(2 SIDES)
BOTTOM VIEW—EXPOSED PAD
NOTE:
1. DRAWING TO BE MADE A JEDEC PACKAGE OUTLINE M0-229 VARIATION OF (WEED-1)
2. DRAWING NOT TO SCALE
3. ALL DIMENSIONS ARE IN MILLIMETERS
4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE
MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE
5. EXPOSED PAD SHALL BE SOLDER PLATED
6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION
ON TOP AND BOTTOM OF PACKAGE
5560f
Information furnished by Linear Technology Corporation is believed to be accurate and reliable.
However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.
27
LT5560
RELATED PARTS
PART NUMBER
DESCRIPTION
COMMENTS
LT5511
High Linearity Upconverting Mixer
RF Output to 3GHz, 17dBm IIP3, Integrated LO Buffer
LT5512
1KHz to 3GHz High Signal Level
Downconverting Mixer
20dBm IIP3, Integrated LO Buffer, HF/VHF/UHF Optimized
LT5514
Ultralow Distortion, IF Amplifier/ADC Driver
with Digitally Controlled Gain
850MHz Bandwidth, 47dBm OIP3 at 100MHz, 10.5dB to 33dB Gain Control Range
LT5515
1.5GHz to 2.5GHz Direct Conversion Quadrature 20dBm IIP3, Integrated LO Quadrature Generator
Demodulator
LT5516
0.8GHz to 1.5GHz Direct Conversion Quadrature 21.5dBm IIP3, Integrated LO Quadrature Generator
Demodulator
LT5517
40MHz to 900MHz Quadrature Demodulator
21dBm IIP3, Integrated LO Quadrature Generator
LT5518
1.5GHz to 2.4GHz High Linearity Direct
Quadrature Modulator
22.8dBm OIP3 at 2GHz, –158.2dBm/Hz Noise Floor, 50Ω Single-Ended LO and
RF Ports, 4-Ch W-CDMA ACPR = –64dBc at 2.14GHz
LT5519
0.7GHz to 1.4GHz High Linearity Upconverting
Mixer
17.1dBm IIP3 at 1GHz, Integrated RF Output Transformer with 50Ω Matching,
Single-Ended LO and RF Ports Operation
LT5520
1.3GHz to 2.3GHz High Linearity Upconverting
Mixer
15.9dBm IIP3 at 1.9GHz, Integrated RF Output Transformer with 50Ω Matching,
Single-Ended LO and RF Ports Operation
LT5521
10MHz to 3700MHz High Linearity
Upconverting Mixer
24.2dBm IIP3 at 1.95GHz, NF = 12.5dB, 3.15V to 5.25V Supply, Single-Ended
LO Port Operation
LT5522
400MHz to 2.7GHz High Signal Level
Downconverting Mixer
4.5V to 5.25V Supply, 25dBm IIP3 at 900MHz, NF = 12.5dB, 50Ω Single-Ended
RF and LO Ports
LT5524
Low Power, Low Distortion ADC Driver with
Digitally Programmable Gain
450MHz Bandwidth, 40dBm OIP3, 4.5dB to 27dB Gain Control
LT5525
High Linearity, Low Power Downconverting
Mixer
50Ω Single-Ended LO and RF Ports, 17.6 dBm IIP3 at 1900MHz, ICC = 28mA
LT5526
High Linearity, Low Power Active Mixer
3V to 5.3V Supply, 16.5dBm IIP3, 100kHz to 2GHz RF, NF = 11dB, ICC = 28mA,
–65dBm LO-RF Leakage
LT5527
400MHz to 3.7GHz High Signal Level
Downconverting Mixer
IIP3 = 23.5dBm and NF = 12.5dB at 1900MHz, 4.5V to 5.25V Supply, ICC = 78mA,
Single-Ended LO and RF Ports
LT5528
1.5GHz to 2.4GHz High Linearity Direct
Quadrature Modulator
21.8dBm OIP3 at 2GHz, –159.3dBm/Hz Noise Floor, 50Ω, 0.5VDC Baseband
Interface, 4-Ch W-CDMA ACPR = –66dBc at 2.14GHz
LT5568
700MHz to 1050MHz High Linearity Direct
Quadrature Modulator
22.9dBm OIP3, –160dBm/Hz Noise Floor, –46dBc Image Rejection,
–43dBm LO Leakage
Infrastructure
RF Power Detectors
LTC®5505
RF Power Detectors with >40dB Dynamic
Range
300MHz to 3GHz, Temperature Compensated, 2.7V to 6V Supply
LTC5507
100kHz to 1000MHz RF Power Detector
100kHz to 1GHz, Temperature Compensated, 2.7V to 6V Supply
LTC5508
300MHz to 7GHz RF Power Detector
44dB Dynamic Range, Temperature Compensated, SC70 Package
LTC5509
300MHz to 3GHz RF Power Detector
36dB Linear Dynamic Range, Low Power Consumption, SC70 Package
LTC5532
300MHz to 7GHz Precision RF Power Detector
Precision VOUT Offset Control, Adjustable Gain and Offset
LT5534
50MHz to 3GHz Log RF Power Detector with
60dB Dynamic Range
±1dB Output Variation over Temperature, 38ns Response Time
LTC5536
Precision 600MHz to 7GHz RF Detector with
Fast Comparater
25ns Response Time, Comparator Reference Input, Latch Enable Input, –26dBm to
+12dBm Input Range
LT5537
Wide Dynamic Range Log RF/IF Detector
Low Frequency to 800MHz, 83dB Dynamic Range, 2.7V to 5.25V Supply
5560f
28 Linear Technology Corporation
LT 0406 • PRINTED IN USA
1630 McCarthy Blvd., Milpitas, CA 95035-7417
(408) 432-1900 ● FAX: (408) 434-0507
●
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© LINEAR TECHNOLOGY CORPORATION 2006