Download 1 Introduction - UVic ECE

Voice Activated Mouse Click
By:
Dylan Hoen
&
Chris Young
Submitted to Dr. Peter Driessen
April 2, 2004
Table of Contents
List of Figures………...…………………………………………………………………....ii
Summary………………...………………………………………………………………...iii
1.0 Introduction ............................................................................................................................... 1
1.1
Purpose of the Project .................................................................................................. 1
1.2
Considering the Options .............................................................................................. 1
2.0 Discussion .................................................................................................................................. 2
2.1
Understanding the Hardware Circuits ........................................................................ 2
2.1.1
Power Supply Circuit .................................................................................................... 2
2.1.2
Analogue Filter Circuit ................................................................................................. 4
2.1.3
System Clock Circuit ..................................................................................................... 7
2.1.4
User Control Circuit ..................................................................................................... 7
2.1.5
Pic to Mouse Circuit ..................................................................................................... 8
2.2
Understanding the 18F258 Series Pic ......................................................................... 9
2.2.1
Reasons for Choosing the Pic ..................................................................................... 9
2.2.2
A/D Converter .............................................................................................................. 9
2.3
System Software............................................................................................................. 9
2.3.1
Software Timing Considerations ............................................................................... 10
2.3.2
Voice Detection Algorithm........................................................................................ 10
3.0 System Testing ......................................................................................................................... 12
3.1.1
Testing the Mouse ....................................................................................................... 12
3.1.2
Software Testing .......................................................................................................... 13
3.1.3
Testing the Mic ............................................................................................................ 14
3.2
Costs of Parts and Accessories .................................................................................. 14
4.0 Using the Device ..................................................................................................................... 15
15
5.0 Conclusions .............................................................................................................................. 16
Cited References…………………………………………………………………………..20
General References………………………………………………………………………..20
Appendix A – Pic 18F258 Features
Appendix B – Pic Software
Appendix C – Software Program Written to Determine the Filter Coefficients
Appendix D – Derivation of High Pass and Low Pass Filter Coefficients
Appendix E – Cost Breakdown
i
List of Figures
Figure 1. Block Diagram of the Device ............................................................................................ 2
Figure 2. Power Supply Circuit .......................................................................................................... 3
Figure 3. Analogue Filter Circuit ....................................................................................................... 4
Figure 4. Simulated Frequency Response of the Analogue Bandpass Filter .............................. 5
Figure 5 System Clock Circuit ........................................................................................................... 7
Figure 6. User Control Circuit .......................................................................................................... 8
Figure 7. Pic to Mouse Circuit .......................................................................................................... 9
Figure 8. Software Algorithm .......................................................................................................... 11
Figure 9. Mouse Power Consumption testing .............................................................................. 12
Figure 10. User Interface ................................................................................................................. 15
ii
Summary
This final report is required for the completion of an undergraduate project course for the
Department of Electrical Engineering at the University of Victoria. The following report
discusses the motivation, research, design and testing of a voice detection device. This device
was created specifically to be integrated into the existing testing software.
This report will discuss the design and testing considerations required in the implementation
of the Voice Activated Mouse. It will also discuss the voice detection algorithm that was
implemented on the PIC. Finally, this report will outline the technical details needed to
properly use the device.
iii
1.0 Introduction
1.1
Purpose of the Project
Verbal Response time to a given stimulus is often required for many psychology
experiments. Many experiments include patients verbally responding to visual stimulus
such as a picture on the computer screen. Often, it is not the actual response that is
important, but the time that it takes for the patient to respond. In the past, patients have
been asked to click a button (or press a key) as they verbally respond so that the response
time could be recorded. For tests involving gestural knowledge and gestural memory
responses, a physical response could distort the results. As a result, a device is required
that would detect a verbal response, and have the ability to transmit a voice detection
signal to a computer, where the response time could be calculated.
1.2 Considering the Options
Two attempts have been made to solve the response time recording problem in the past,
neither of which worked particularly well.
According to Mike Mason (chair of the UVic Psychology department) an external device
was created 4 years ago that was too noise sensitive to be effective. It was basically a
threshold trigger device in which the any sound above a certain level would set it off. The
department encountered problems when typical testing environment sounds (example:
moving chair, outside sounds, footsteps) would be interpreted as a voice response. To
make matters worse, the device would only work on computers that had the old
Macintosh mouse connector, which has now been replaced by new USB mice.
The second attempt involved using the existing mic and communication hardware that
comes with Mac computers. A program was written to detect voice responses and return
the response time to the testing software. This program worked well in quiet testing
environments, but when they tried to demo it at a conference, the background noise
(human voices) severely affected the detection accuracy. Furthermore, the voice
detection program (that worked with the mic) would have to be specifically modified to
work with computers that have either a different operating system and/or
communication hardware. The current setup will need to be drastically modified to be
compatible with G5 computers and the Mac Os X operating system.
The problems that the other devices encountered were carefully examined and considered
when the Voice Activated Mouse Click was created. We built is so that would work with
all computers, have an accurate voice detection algorithm in a noisy or quiet environment,
and give the user greater control over important device parameters. In addition, itis
powered completely through USB power, thus, giving the user freedom of using the
device on a laptop without having an external power supply.
1
2.0 Discussion
2.1 Understanding the Hardware Circuits
A device was build consisting of several circuits attached to a Logitech USB mouse.
These circuits included: an analogue filter circuit, power supply circuit, system clock,
user input circuit, Pic to Mouse-Click circuit, and a LED display circuit. The device
detects human voice in noisy environments, and causes the computer to interpret the
voice as a mouse click. By connecting the voice detection device to the Logitech
mouse, the device can be used on almost every computer available (both Mac and PC).
The computer will not have to recognize the additional voice detection circuits added
to the mouse, thus, the device will work on most computers (assuming that the
appropriate drivers are installed).
Figure 1. Block Diagram of the Device
2.1.1 Power Supply Circuit
The device was designed in such a way that it would be completely powered through a USB
connection, thus, eliminating the need for an external power source when used on a laptop.
A circuit was built to give us a larger voltage range (including a negative voltage) because the
typical USB voltage range 0-5V would not be sufficient. Our input signal was very close to 0
volts therefore we needed to create a negative voltage to power the op amps. If a zero
voltage reference was used (that wasn’t ground), we wouldn’t have enough impedance and
2
noise would flow back into the ground wire. This problem was eliminated by generating a
-3V supply, which was used for the negative Op-Amp power supply and ground was used as
the 0 volt reference.
After the signal had been amplified by a factor of 100 and filtered, it was passed to another
Op-Amp circuit using 2.048 volts as its ground. We had to do this because the pic
microcontroller would not except negative voltages through it’s A/D converter. A stable
4.096 voltage IC was used as the A/D reference voltage for the pic (2.048V is exactly half of
4.096V allowing for equal positive and negative voltage swing).
Our capacitor charge pump power supply generated a lot of noise in its output voltages and
also sent noise back through its power input to the rest of the circuit. The power supply was
run at 10 KHz because it operates most efficiently at that value. When switching the
capacitors between series and parallel, we found that it caused current surges and voltage
jumps at a rate of 10 KHz (that was amplified at a factor of 1000 by our audio amplifier
circuit) giving us a very poor signal to noise ratio. In attempt to improve the signal to noise
ratio, we filtered the output with an RC filter circuit using fairly large (4700uF) capacitors
and small (10 ohm) resistors. When this circuit was tested, it was determined that the signal
to noise ratio was even worse. After some investigation we found that the power supply was
sending noise back through its power input and into the power supply for the rest of the
circuits. We used another RC filter (10ohms / 100uf) to filter out this noise and obtain a
much better signal to noise ratio. We discovered that the power supply produced an
adequate amount of power at 100 KHz, therefore, the power supply was changed to 100
KHz, which greatly reduced the amount of noise in the circuit.
Figure 2. Power Supply Circuit
3
2.1.2 Analogue Filter Circuit
The band pass filter was designed to let the common frequencies of the human voice
through (150Hz-4500Hz) while eliminating the 60Hz noise (that is common around most
computers) and frequencies above our 10kHz nyquist sampling frequency. The sound was
picked up from a speaker and the signal was sent through an audio transformer, increasing
the voltage. The signal was amplified by a factor of 100 then it was put through a 4 th order
high pass and a 4th order low pass filter. The signal was then stepped up from a ground of
zero volts to a virtual ground of 2.048 volts and put through a user-adjustable amplifier. It
was then read through the A/d converter where it was processed in software.
Figure 3. Analogue Filter Circuit
4
Figure 4. Simulated Frequency Response of the Analogue Bandpass Filter
The first plot in Figure 4 shows the strength of the signal in dB. The second plot shows the
aliasing noise level for various frequencies in dB (valid for frequencies less than the 10 KHz
Nyquist sampling frequency). The third plot shows the phase, but it might not be accurate
due to certain limitations in the demo version of Micro Cap 7 simulation software. The
fourth plot is the signal transmitted as a fraction of the original signal. The fifth plot is the
aliasing noise as a fraction of the original signal amplitude (valid for frequencies less than the
10 KHz Nyquist sampling frequency).
2.1.2.1
Testing of the Analogue filter Circuit Using an Oscilloscope
When testing the band pass filter on batteries, the circuit worked fine, but when tested on a
power supply, we got a large 60 Hz noise signal. The high pass filter corner frequency had
to be raised from the original 40 Hz to 120 Hz to solve this problem.
The analogue filter was hooked up to a sine wave generator and an oscilloscope in order to
ensure that it had a reasonable frequency response. Initial tests revealed that the filter had:

a peak at 1.5KHz

-3dB points at 500Hz and 4 KHz

-6dB points at 400Hz and 5.8KHz
5
At 120Hz the signal was virtually non-existent. In order to ensure that lower voice
frequencies were not filtered out (and that the 60Hz noise was completely eliminated), we
changed several of the filter parameters. The final frequency response is as follows:

1.3 KHz peak

-3 dB at 260 Hz and 3.6 KHz

-6 dB at 210 Hz and 5.2 KHz

-12 dB at 180 Hz and 8.7 KHz

-18 dB at 134 Hz and 11.4 KHz
60 Hz :
Peak of 2 Volts at 1.3KHz
1
 0.050 
 2  = 0.025 = 40
20 log(0.025)  32.04dB
Other points of interest were tested to ensure that there was no aliasing:
at 10KHz :
measured amplitude  peak amplitude
 400mV  2V
 0.2
20 log(0.2)  13.9794dB
If we were looking at a 5 KHz signal:
The original software routine had band pass filters that had a range of  or  2 , therefore
we had to look at the frequency with the highest aliasing noise in that range.
5KHz 
2  7071Hz
Aliasing would occur at: 20KHz  7KHz  13KHz
at 13KHz :
measured amplitude  peak amplitude
 230mV  2V
 0.115
20 log(0.115)  18.786dB
6
Results indicate that the aliasing components and noise are at acceptable levels.
2.1.3
System Clock Circuit
This is the minimum amount of wiring and support components needed to operate a pic
microcontroller.
Figure 5 System Clock Circuit
(We could not locate any ceramic resonators so we constructed the following circuit for our
clock.)
2.1.4 User Control Circuit
This section outlines the user-controlled aspects of the device. There are several dials and
buttons that give the user control over things such as gain, response time, and
enable/disable mouse click.
The dials are connected to potentiometers that are connected to a stable 4.096V reference
and to ground. The A/D converters reference voltage also connected to the 4.096V voltage.
The value is read as an integer between 0 and 255, linearly proportional to the amount that
the potentiometer has been turned. The program maps the 0-255 value to a set of discrete
predefined vales which it uses for processing.
7
Figure 6. User Control Circuit
Buttons and switches were also on the device. These buttons include enable/disable of the
clicking, voice training, and background noise training. These buttons connect a TTL input
pin to +5 Volts when pressed. These pins are normally connected to ground through a 10K
resistor.
2.1.5 Pic to Mouse Circuit
This section outlines the signal connection between the voice detection device and the USB
mouse. When the program decides to click the mouse, it sends a positive signal to the base
of the transistor, which switches the transistor on. When the transistor is turned on, it
connects the mouse button to ground causing a mouse click.
8
Figure 7. Pic to Mouse Circuit
2.2 Understanding the 18F258 Series Pic
2.2.1 Reasons for Choosing the Pic
The software was originally written for a 16F876A pic, but since it does not have a hardware
multiplier, we were unable to do any complex software routines on it. As a result, it was
decided that a more powerful 18 series pic would be used.
A 18F258 pic was used because it had the ability to use 4 A/D converters with an external
voltage reference. It also has a timer for precise sampling periods, which is required for a
digital filter. The pic had sufficient I/O pins that were used for button input and LED
output. This pic is a relatively compact component that would fit nicely into our circuit. It
met our limited power requirements (5 V and 200mA shared between the circuit and the
mouse). Refer to Appendix A for the feature set of the 18F258.
2.2.2 A/D Converter
The A/D converter was used to read in the voice signal and the positions of the user
controlled dials. An external 4.096 V reference was used for stable A/D reads to avoid
power supply noise. The chip has a 10 bit A/D converter but it was set to 8 bit mode so
that we could use 8 bit numbers to avoid using unnecessary clock cycles in the
computations. The chip has an 8 by 8 hardware multiply that was used extensively in the
algorithm.
2.3 System Software
9
2.3.1 Software Timing Considerations
The entire human voice spectrum had to be captured so we need to analyze frequencies as
high as 5 KHz. In order to avoid aliasing, we either had to sample at 20 KHz or create a
sharper low pass filter. We opted to use the 20 KHz sampling frequency. A 20 MHz clock
crystal was used to drive the pic. The pic divides the clock frequency by four, thus, giving us
a 5MHz instruction rate which allows for approximately 250 instructions per A/D sample.
The algorithm was programmed in the C language; therefore, many of the instructions were
used up as load and store instructions. It is estimated that ¼ of the instructions were
available to do the multiplying, adding, comparing, and decision-making. It was impossible
to implement many of the voice detection routines that we initially intended on using
because of the low instruction count constraint.
It is possible to run a PIC18F258 at 40 MHz using a 40 MHz clock or a 10 MHz clock in a 4
times phase lock loop mode but these clock crystals were not in stock at the local electronics
stores. In addition, we tested the clock at the 4 x 20 clock speed and noticed that it actually
ran at about 60MHz, showing that the phase lock loop was unstable at this speed. Had we
implemented this over clocking, our results would have been inconsistent and probably
temperature dependant.
2.3.2 Voice Detection Algorithm
Five software band pass filters were used to filter the incoming signal. Each of these band
pass filters were connected to 2 envelope detectors, which work at different speeds. The fast
envelope detector was used to mark the time of the start of the voice and the slow envelope
detector identifies if it is the target voice or not. A value will be obtained from each of the 5
fast and 5 slow envelope detectors, which will be compared with similar values stored in
memory. These stored values are obtained when the device is put in training mode and
samples of background noise and target voice are processed in a similar way as the above.
During the comparison, a "vote" process occurs (best 3/5) to determine if the sampled
signal is more similar to the voice sample than the background noise sample. The fast
envelope detector vote starts a timer. If a subsequent vote is false, the timer is reset. If the
slow envelope detector vote determines that the signal is the target voice, the device waits
for the timer to count up to a predefined value (user controllable), then a mouse click will
occur. The psychology program adjusts for this user-defined time lapse when determining
the exact response time.
When the device is triggered it sends a mouse click signal to the computer. Once this is
done, the device will wait a certain amount of time (this wait time is determined by the user
controls) before it is ready to detect another signal.
10
Figure 8. Software Algorithm
In figure 7, the boxes represent partially-overlapping band pass filters.
frequency is half of the target frequency of the previous band pass filter.
11
Each target
3.0 System Testing
3.1.1
Testing the Mouse
3.1.1.1
Determining the Mouse Power Consumption
The mouse was taken apart and rewired enabling us to determine its USB power
consumption. It is important that we had sufficient power to operate the mouse and voice
detection device simultaneously. It was determined that the mouse uses 29mA in the stand
by mode, and 52mA when the mouse is tracking (the LED gets brighter). These values are
much lower than what we had initially predicted. The remaining 148mA (USB max is
typically 200mA) is more than sufficient to operate the voice detection device.
Figure 9. Mouse Power Consumption testing
12
3.1.2 Software Testing
We wrote a program in Java to determine the first order and second order filter coefficients
for the high pass and low pass filters. This program starts with a specific sine wave and its
amplitude was recorded. This sine wave was put through the filter with a variable input
coefficient and the resulting amplitude was compared to the original amplitude. The
Coefficients were adjusted based on whether the amplitude was higher or lower than 3 dB
from the original and the process was repeated 20 times. The coefficients of the final run
20
1
1
through were accurate to a factor of    6 . The test was repeated for each of the
10
2
target frequencies. The results of these tests are as follows:
Refer to Appendix C for the Source Code.
Low Pass Filter Coefficient Results
y(t )  c  x(t )  1  c   y(t 1)
y2 (t )  c  y(t )  1  c   y2 (t 1)
4 sample/cycle:
First order 3DB ratio = 0.7509617805480957
First order 6DB ratio = 0.5857863426208496
Second order 3DB ratio = 0.864356517791748
Second order 6DB ratio = 0.7667346000671387
8 sample/cycle:
First order 3DB ratio = 0.5857863426208496
First order 6DB ratio = 0.35640573501586914
Second order 3DB ratio = 0.6944746971130371
Second order 6DB ratio = 0.5298819541931152
16 sample/cycle:
First order 3DB ratio = 0.3318209648132324
First order 6DB ratio = 0.20199346542358398
Second order 3DB ratio = 0.4498744010925293
Second order 6DB ratio = 0.3215975761413574
32 sample/cycle:
First order 3DB ratio = 0.1793208122253418
First order 6DB ratio = 0.10701799392700195
Second order 3DB ratio = 0.26179075241088867
Second order 6DB ratio = 0.1777663230895996
64 sample/cycle:
First order 3DB ratio = 0.09365320205688477
13
First order 6DB ratio = 0.055086612701416016
Second order 3DB ratio = 0.14140748977661133
Second order 6DB ratio = 0.09343862533569336
High Pass Filter Coefficient Results
n0  c
n1  c
d 0  (c  1)
d1  c  1
y (t ) 
n0  x(t )  n1  x(t  1)  d1 y (t  1)
d0
4 sample/cycle:
First order 3DB ratio = 1.5537397589683533
8 sample/cycle:
First order 3DB ratio = 2.414218051433563
16 sample/cycle:
First order 3DB ratio = 5.02737563085556
32 sample/cycle:
First order 3DB ratio = 10.15314115381241
64 sample/cycle:
First order 3DB ratio = 20.355483129024506
Refer to Appendix D to see the derivation of the formula for this high pass filter.
3.1.3 Testing the Mic
The microphone that we had originally purchased did not work to our standards. The
signal that it would produce was much too weak when compared to the noise level in the
circuit. As a result, we obtained an internal computer speaker to use as the input device.
It was determined that this speaker had an impedance of 8 ohms. The speaker was
connected to an audio transformer that had 8 ohm impedance on one side and 1.2k on
the other. A Plexiglas box was built around the speaker in order to maximize its sound
collecting ability and it was suspended on a coat hanger wire to reduce the vibrations
transmitted to it through the table.
3.2
Costs of Parts and Accessories
The complete cost of the voice activated mouse click was found to be $182.12. See
appendix E for a breakdown of the cost of the parts.
14
4.0 Using the Device
Figure 10. User Interface
The following are the necessary steps to use the device:
1. As soon as the device is plugged into the USB port of most computers, the operating
system will automatically detect the device and install the drivers for the mouse.
Initially the device should be switched into disabled mode.
2. Adjust the trigger time and the reset time dials to your preferred values. While saying
“aahhhhh” adjust the gain so that the green LED (labeled “Good Gain”) lights up
while making sure that the red LED (labeled “Gain Too High”) doesn’t light. This
ensures that the voice signal is at an appropriate level for the software analyzer.
3. While being as quiet as possible, push the button that is labeled “Train Back Ground
Noise Level”.
4. While saying “ahhhh” at a normal speaking level, press the “Train Voice” button. A
sample of the state of all of the filters is taken at the exact moment that the button is
pushed.
5. The device has now been trained and it is ready to be enabled by flipping the switch
into the enabled position. The device will now click when it detects the target voice.
15
5.0 Conclusions
This project involved in depth research and intensive problem solving. It was more complex
than what we had originally thought and it involved implementing knowledge in areas such
as digital signal processing, communications, electronic devices, analogue filters,
microcontrollers, java and C programming, and hardware. Though we experienced many set
backs and design changes, we are happy to say that the final product exceeded the
performance expectations outlined by the psychology department. Even though long hours
were spent overcoming the numerous challenges we encountered, the sense of
accomplishment that we received made it well worth it. The practical knowledge that we
have gained this assignment goes way beyond the classroom.
16
Cited References
[1]. “The Bypass Capacitor in High-Speed Environments.” Texas Instruments,
November 1996, Application Report, literature number SCBA007A. (1 March 2001).
[2] "Digital Filter Design Writing Difference Equations For Digital Filters" Brian T. Boulter,
[Online serial] (2000), Available at: http://www.apicsllc.com/apics/Sr_3/Sr_3.htm
General References
Ghaemmaghami, S.; Deriche, M.; Boashash, B.;
TENCON '97. IEEE Region 10 Annual Conference. Speech and Image Technologies for
Computing and Telecommunications'., Proceedings of IEEE , Volume: 2 , 2-4 Dec. 1997
Pages:743 - 746 vol.2
Ngoc Bui; Monbaron, J.; Michel, J.;
Acoustics, Speech, and Signal Processing [see also IEEE Transactions on Signal Processing],
IEEE Transactions on , Volume: 31 , Issue: 1 , Feb 1983
Pages:323 - 329
McAulay, R.J.; Quatieri, T.F.;
Acoustics, Speech, and Signal Processing, 1990. ICASSP-90., 1990 International Conference
on , 3-6 April 1990 Pages:249 - 252 vol.1
17
APPENDIX A
Pic 18F258 Features
18
19
APPENDIX B
Pic Software
20
APPENDIX C
Software Program Written to Determine the Filter Coefficients
21
APPENDIX D
Derivation of High Pass and Low Pass Filter Coefficients
Theory taken from [2]:
http://www.apicsllc.com/apics/Sr_3/Sr_3.htm
22
2nd Order Low-Pass Filter
4 samples / cycle (5 KHz )
196  new  60  old
8 samples / cycle (2.5 KHz )
136  new  120  old
16 samples / cycle (1.25 KHz )
82  new  174  old
32 samples / cycle (0.625 KHz )
196  new  60  old
64 samples / cycle (0.3125 KHz )
24  new  232  old
23
2nd Order High-Pass Filter
n0  n1 z 1  n1 z 2
H ( z) 
d0  d1 z -1  d 2 z -2
Y  HX
Y (d 0  d1 z 1  d 2 z 2 )  (n0  n1 z 1  n2 z 2 ) X
d 0Y (t )  d1Y (t  1)  d 2Y (t  2)  n0 X (t )  n1 X (t  1)  n2 X (t  2)
Y (t ) 
n0 X (t )  n1 x(t  1)  n2 X (t  2)  d1Y (t  1)  d 2Y (t  2)
d0
CX (t )  CX (t  1)  (C  1)Y (t  1)
C 1
 C 
 C 
 C 1 
Y (t )  
 X (t )  
 X (t  1)  
 Y (t  1)
 C 1 
 C 1
 C 1
cycles
  2


sec


sec


t
C=cot 

sample
 sample  
 

cycle  
t  cycle





2 sample  sample 
 cycle 


For n=2
n0  1
Y (t ) 
n1  2
n2  1
d0  2  C 2  1
d1  2  C 2  1
d2   2  C 2  1
1st Order High-Pass Filter
The high pass difference equation is obtained from the normalized Butterworth continuous
time filter descriptions given below.
1st. order normalized Butterworth low pass filter:
1
H (s) 
(1)
s 1
The above low pass equation is mapped to the appropriate filter type using the following
mapping:
24
s
hc
;
dc
hc = desired high-pass 3 [dB] pass frequency.
where:
B = A number that controls the notch depth/width (equivalent to 1/Q).
cc = The desired continuous time center frequency.
To create a digital filter we normalize the above filter by setting cc = 1, and map to the zdomain using the bi-linear transformation:
 z 1 
swcc  c  
 (2)
 z 1
The c co-efficient in the above equation is used to accomplish frequency warping. That is, to
compensate for an inherent inaccuracy in the bi-linear transformation method that is a
function of frequency and sample rate. Once the above mapping is performed by
substituting (2) into the continuous time s-domain filter equation we obtain a z-domain
transfer function of the form:
H ( z) 
n0  n1 z 1 
d0  d1 z 1 
 nn z  n
 dd z d
For n=1
n0  C
n1  C
d 0  (C  1)
d1  C  1
Filter Coefficients
4 samples / cycle  C  1.5020
0.6003
-0.6003 0.2006
154,-154,51
8 samples / cycle  C  2.6784
0.7277
-0.7272 0.455397
186,-186,117
16 samples / cycle  C  5.1577
0.8376
-0.8376 0.6752
214,-214,173
32 samples / cycle  C  10.2186
0.91086
-0.91086 0.82172
64 samples / cycle  C  20.3882
0.95325
-0.95325 0.90649
233,-233,210
244,-244,232
25
(3)
APPENDIX E
Cost Break down
COMPONENT
DESCRIPTION
Pic 18F258
10K resistors
Capacitors
USB mouse
Logitech
logarithmic
50K
potentiometer
50 K linear potentiometer
QUANTITY
2
21
18
1
COST
$4.10
$0.30
$0.50
$42.13
1
$3.25
1
$2.60
10 K linear potentiometer
5K linear potentiometer
20 MHZ Crystal
1
1
1
$2.60
$2.60
$8.14
Max 660
Germanium Diodes
Max 6341
Lm 348 quad 741 op amp
ICs
741 op amp IC
Speaker to use as a Mic
dials
LED's
Breadboard
Device Protective Container
Capacitor Charge pump voltage
doublers and negative voltage power 1
supply
2
4.096 V reference
2
Internal computer speaker
Lower power, super bright
Oversized
Container was built with Plexiglas
Grand Total
$6.10
$0.45
$4.50
2
$4.00
1
1
5
8
1
1
$3.10
$4.50
$0.90
$0.80
$48.80
$6.00
$182.12
26