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®
RCV420
RCV
420
Precision 4mA to 20mA
CURRENT LOOP RECEIVER
FEATURES
APPLICATIONS
● COMPLETE 4-20mA TO 0-5V CONVERSION
● PROCESS CONTROL
● INTERNAL SENSE RESISTORS
● PRECISION 10V REFERENCE
● BUILT-IN LEVEL-SHIFTING
● INDUSTRIAL CONTROL
● FACTORY AUTOMATION
● DATA ACQUISITION
● ±40V COMMON-MODE INPUT RANGE
● 0.1% OVERALL CONVERSION ACCURACY
● HIGH NOISE IMMUNITY: 86dB CMR
● SCADA
● RTUs
● ESD
● MACHINE MONITORING
DESCRIPTION
transmitter compliance voltage is at a premium. The
10V reference provides a precise 10V output with a
typical drift of 5ppm/°C.
The RCV420 is a precision current-loop receiver designed to convert a 4–20mA input signal into a 0–5V
output signal. As a monolithic circuit, it offers high
reliability at low cost. The circuit consists of a premium grade operational amplifier, an on-chip precision
resistor network, and a precision 10V reference. The
RCV420 features 0.1% overall conversion accuracy,
86dB CMR, and ±40V common-mode input range.
The RCV420 is completely self-contained and offers a
highly versatile function. No adjustments are needed
for gain, offset, or CMR. This provides three important
advantages over discrete, board-level designs: 1) lower
initial design cost, 2) lower manufacturing cost, and
3) easy, cost-effective field repair of a precision circuit.
The circuit introduces only a 1.5V drop at full scale,
which is useful in loops containing extra instrument
burdens or in intrinsically safe applications where
V+
V–
Ref In
16
4
12
RCV420
300kΩ
–In
92kΩ
11.5kΩ
99kΩ
1
15 Rcv fB
RS
75Ω
CT
11 Ref Out
2
RS
75Ω
+In
14 Rcv Out
+10V
Ref
1.01kΩ
3
300kΩ
100kΩ
13
5
Rcv
Com
Ref
Com
10 Ref fB
8
Ref Trim
7
Ref Noise Reduction
International Airport Industrial Park • Mailing Address: PO Box 11400, Tucson, AZ 85734 • Street Address: 6730 S. Tucson Blvd., Tucson, AZ 85706 • Tel: (520) 746-1111 • Twx: 910-952-1111
Internet: http://www.burr-brown.com/ • FAXLine: (800) 548-6133 (US/Canada Only) • Cable: BBRCORP • Telex: 066-6491 • FAX: (520) 889-1510 • Immediate Product Info: (800) 548-6132
®
©
1988 Burr-Brown Corporation
SBVS019
PDS-837E
1
RCV420
Printed in U.S.A. October, 1997
SPECIFICATIONS
ELECTRICAL
At T = +25°C and VS = ±15V, unless otherwise noted.
RCV420KP, JP
CHARACTERISTICS
MIN
TYP
GAIN
Initial
Error
Error—JP Grade
vs Temp
Nonlinearity(1)
0.3125
0.05
15
0.0002
OUTPUT
Rated Voltage (IO = +10mA, –5mA)
Rated Current (EO = 10V)
Impedance (Differential)
Current Limit (To Common)
Capacitive Load
(Stable Operation)
INPUT
Sense Resistance
Input Impedance (Common-Mode)
Common-Mode Voltage
CMR(2)
vs Temp (DC) (TA = TMIN to TMAX)
AC 60Hz
OFFSET VOLTAGE (RTO)(3)
Initial
vs Temp
vs Supply (±11.4V to ±18V)
vs Time
10
+10, –5
MAX
0.15
0.25
0.002
12
75
200
70
80
76
80
75.75
±40
ZERO ERROR(4)
Initial
Initial—JP Grade
vs Temp
0.025
Ω
kΩ
V
dB
dB
dB
1
mV
µV/°C
dB
µV/mo
0.075
0.15
% of span
% of span
ppm of
span/°C
10
90
200
74
V/mA
% of span
% of span
ppm/°C
% of span
V
mA
Ω
mA
pF
0.01
+49, –13
1000
74.25
UNITS
10
OUTPUT NOISE VOLTAGE
fB = 0.1Hz to 10Hz
fO = 10kHz
50
800
µVp-p
nV/√Hz
DYNAMIC RESPONSE
Gain Bandwidth
Full Power Bandwidth
Slew Rate
Settling Time (0.01%)
150
30
1.5
10
kHz
kHz
V/µs
µs
VOLTAGE REFERENCE
Initial
Trim Range(5)
vs Temp
vs Supply (±11.4V to ±18V)
vs Output Current (IO = 0 to +10mA)
vs Time
Noise (0.1Hz to 10Hz)
Output Current
POWER SUPPLY
Rated
Voltage Range(6)
Quiescent Current (VO = 0V)
TEMPERATURE RANGE
Specification
Operation
Storage
Thermal Resistance, θJA
9.99
10.01
±4
5
0.0002
0.0002
15
5
+10, –2
±15
–5, +11.4
3
0
–25
–40
±18
4
+70
+85
+85
80
V
%
ppm/°C
%/V
%/mA
ppm/kHz
µVp-p
mA
V
V
mA
°C
°C
°C
°C/W
NOTES: (1) Nonlinearity is the max peak deviation from best fit straight line. (2) With 0 source impedance on Rcv Com pin. (3) Referred to output with all inputs
grounded including Ref In. (4) With 4mA input signal and Voltage Reference connected (includes VOS, Gain Error, and Voltage Reference Errors). (5) External trim
slightly affects drift. (6) IO Ref = 5mA, IO Rcv = 2mA.
®
RCV420
2
ABSOLUTE MAXIMUM RATINGS(1)
PIN CONFIGURATION
Top View
DIP
–In
1
16
V+
CT
2
15
Rcv fB
+In
3
14
Rcv Out
V–
4
13
Rcv Com
Ref Com
5
12
Ref In
NC
6
11
Ref Out
Ref Noise Reduction
7
10
Ref fB
Ref Trim
8
9
NC
Supply ............................................................................................... ±22V
Input Current, Continuous ................................................................ 40mA
Input Current Momentary, 0.1s ........................... 250mA, 1% Duty Cycle
Common-Mode Input Voltage, Continuous ....................................... ±40V
Lead Temperature (soldering, 10s) ............................................... +300°C
Output Short Circuit to Common (Rcv and Ref) ..................... Continuous
NOTE: (1) Stresses above these ratings may cause permanent damage.
PACKAGE INFORMATION
PRODUCT
PACKAGE
PACKAGE DRAWING
NUMBER(1)
RCV420KP
RCV420JP
16-Pin Plastic DIP
16-Pin Plastic DIP
180
180
NOTE: (1) For detailed drawing and dimension table, please see end of data
sheet, or Appendix C of Burr-Brown IC Data Book.
ORDERING INFORMATION
PRODUCT
PERFORMANCE
GRADE
PACKAGE
RCV420KP
RCV420JP
0°C to +70°C
0°C to +70°C
16-Pin Plastic DIP
16-Pin Plastic DIP
The information provided herein is believed to be reliable; however, BURR-BROWN assumes no responsibility for inaccuracies or omissions. BURR-BROWN assumes
no responsibility for the use of this information, and all use of such information shall be entirely at the user’s own risk. Prices and specifications are subject to change
without notice. No patent rights or licenses to any of the circuits described herein are implied or granted to any third party. BURR-BROWN does not authorize or warrant
any BURR-BROWN product for use in life support devices and/or systems.
®
3
RCV420
TYPICAL PERFORMANCE CURVES
At TA = +25°C, VS = ±15V, unless otherwise noted.
STEP RESPONSE
NO LOAD
SMALL SIGNAL RESPONSE
RL = ∞, CL = 1000pF
SMALL SIGNAL RESPONSE
NO LOAD
POSITIVE COMMON-MODE VOLTAGE RANGE
vs POSITIVE POWER SUPPLY VOLTAGE
NEGATIVE COMMON-MODE VOLTAGE RANGE
vs NEGATIVE POWER SUPPLY VOLTAGE
–80
Negative Common-Mode Range (V)
Positive Common-Mode Range (V)
80
TA = –55°C
70
TA = +25°C
60
TA = +125°C
50
Max Rating = 40V
40
–VS = –5V to –20V
–70
TA = +25°C
–60
–50
Max Rating = –40V
TA = –55°C to +125°C
–40
–30
+VS = +11.4V to +20V
–20
–10
30
11
12
11.4
13
14
15
16
17
18
19
–5
20
–10
–20
–15
Positive Power Supply Voltage (V)
Negative Power Supply Voltage (V)
COMMON-MODE REJECTION
vs FREQUENCY
POWER-SUPPLY REJECTION
vs FREQUENCY
100
100
90
80
PSR (dB)
CMR (dB)
80
60
V+
V–
60
40
40
1
10
100
1k
10k
100k
1
Frequency (Hz)
100
1k
Frequency (Hz)
®
RCV420
10
4
10k
100k
necessary level shifting. If the Ref In pin is not used for level
shifting, then it must be grounded to maintain high CMR.
THEORY OF OPERATION
Refer to the figure on the first page. For 0 to 5V output with
4–20mA input, the required transimpedance of the circuit is:
GAIN AND OFFSET ADJUSTMENT
VOUT /IIN = 5V/16mA = 0.3125V/mA.
Figure 2 shows the circuit for adjusting the RCV420 gain.
Increasing the gain of the RCV420 is accomplished by
inserting a small resistor in the feedback path of the amplifier. Increasing the gain using this technique results in CMR
degradation, and therefore, gain adjustments should be kept
as small as possible. For example, a 1% increase in gain is
typically realized with a 125Ω resistor, which degrades
CMR by about 6dB.
To achieve the desired output (0V for 4mA and 5V for
20mA), the output of the amplifier must be offset by an
amount:
VOS = –(4mA)(0.3125V/mA) = –1.25V.
The input current signal is connected to either +In or –In,
depending on the polarity of the signal, and returned to
ground through the center tap, CT. The balanced input—two
matched 75Ω sense resistors, RS—provides maximum rejection of common-mode voltage signals on CT and true differential current-to-voltage conversion. The sense resistors
convert the input current signal into a proportional voltage,
which is amplified by the differential amplifier. The voltage
gain of the amplifier is:
A decrease in gain can be achieved by placing matched
resistors in parallel with the sense resistors, also shown in
Figure 2. The adjusted gain is given by the following
expression
VOUT/IIN = 0.3125 x RX /(RX + RS).
A 1% decrease in gain can be achieved with a 7.5kΩ
resistor. It is important to match the parallel resistance on
each sense resistor to maintain high CMR. The TCR mismatch between the two external resistors will effect gain
error drift and CMR drift.
AD = 5V/(16mA)(75Ω) = 4.1667V/V.
The tee network in the feedback path of the amplifier
provides a summing junction used to generate the required
–1.25V offset voltage. The input resistor network provides
high-input impedance and attenuates common-mode input
voltages to levels suitable for the operational amplifier’s
common-mode signal capabilities.
There are two methods for nulling the RCV420 output offset
voltage. The first method applies to applications using the
internal 10V reference for level shifting. For these applica-
BASIC POWER SUPPLY
AND SIGNAL CONNECTIONS
–In
Figure 1 shows the proper connections for power supply and
signal. Both supplies should be decoupled with 1µF tantalum capacitors as close to the amplifier as possible. To avoid
gain and CMR errors introduced by the external circuit,
connect grounds as indicated, being sure to minimize ground
resistance. The input signal should be connected to either
+In or –In, depending on its polarity, and returned to ground
through the center tap, CT. The output of the voltage reference, Ref Out, should be connected to Ref In for the
IIN
4–20mA
+In
3
CT
2
–In
RS
75Ω
RS
75Ω
1
200Ω(1)
CT
+In
10kΩ(1)
10kΩ(1)
RX
1µF
V–
14
RCV420
Rcv Out
3
FIGURE 2. Optional Gain Adjustment.
+10V
Reference
4
±0.5% Gain
Adjustment
NOTE: (1) Typical values. See text.
1
16
2
RX
RCV420
V+
R1
15
13
Rcv Com
12
Ref In
15
Rcv fB
14
11
Rcv Out
Ref Out
10
8
7
VO
(0–5V)
Ref fB
Ref Trim
Ref Noise Reduction
5
Ref Com
1µF
FIGURE 1. Basic Power Supply and Signal Connections.
®
5
RCV420
tions, the voltage reference output trim procedure can be
used to null offset errors at the output of the RCV420. The
voltage reference trim circuit is discussed under “Voltage
Reference.”
using the Rcv Com pin. It is important to use a low-output
impedance amplifier to maintain high CMR. With this method
of zero adjustment, the Ref In pin must be connected to the
Rcv Com pin.
When the voltage reference is not used for level shifting or
when large offset adjustments are required, the circuit in
Figure 3 can be used for offset adjustment. A low impedance
on the Rcv Com pin is required to maintain high CMR.
MAINTAINING COMMON-MODE REJECTION
Two factors are important in maintaining high CMR: (1)
resistor matching and tracking (the internal resistor network
does this) and (2) source impedance. CMR depends on the
accurate matching of several resistor ratios. The high accuracies needed to maintain the specified CMR and CMR
temperature coefficient are difficult and expensive to reliably achieve with discrete components. Any resistance imbalance introduced by external circuitry directly affects
CMR. These imbalances can occur by: mismatching sense
resistors when gain is decreased, adding resistance in the
feedback path when gain is increased, and adding series
resistance on the Rcv Com pin.
ZERO ADJUSTMENT
Level shifting the RCV420 output voltage can be achieved
using either the Ref In pin or the Rcv Com pin. The
disadvantage of using the Ref In pin is that there is an 8:1
voltage attenuation from this pin to the output of the RCV420.
Thus, use the Rcv Com pin for large offsets, because the
voltage on this pin is seen directly at the output. Figure 4
shows the circuit used to level-shift the output of the RCV420
–In
1
CT
2
The two sense resistors are laser-trimmed to typically match
within 0.01%; therefore, when adding parallel resistance to
decrease gain, take care to match the parallel resistance on
each sense resistor. To maintain high CMR when increasing
the gain of the RCV420, keep the series resistance added to
the feedback network as small as possible. Whether the Rcv
Com pin is grounded or connected to a voltage reference for
level shifting, keep the series resistance on this pin as low as
possible. For example, a resistance of 20Ω on this pin
degrades CMR from 86dB to approximately 80dB. For
applications requiring better than 86dB CMR, the circuit
shown in Figure 5 can be used to adjust CMR.
15
+In
14
RCV420
VO
5
3
13
+15V
12
OPA237
100kΩ
100kΩ
±150mV adjustment at output.
1kΩ
PROTECTING THE SENSE RESISTOR
The 75Ω sense resistors are designed for a maximum continuous current of 40mA, but can withstand as much as
250mA for up to 0.1s (see absolute maximum ratings).
There are several ways to protect the sense resistor from
–15V
FIGURE 3. Optional Output Offset Nulling Using External
Amplifier.
–In
Use 10V Ref for +
and 10V Ref with INA105 for –.
1
15
CT
+In
2
VO = (0.3125)(I IN ) + V ZERO
14
RCV420
VO
13
11
3
10
1kΩ
2
5
13
+10V
3
5
INA105
12
Procedure:
1. Connect CMV to C T.
2. Adjust potentiometer for near zero
at the output.
RCV420
6
1kΩ
–10V
1
OPA237
V ZERO
200Ω
CMR
Adjust
1kΩ
OPA237
±5V adjustment
at output.
10kΩ
1kΩ
50kΩ
10kΩ
FIGURE 4. Optional Zero Adjust Circuit.
FIGURE 5. Optional Circuit for Externally Trimming CMR.
®
RCV420
6
overcurrent conditions exceeding these specifications. Refer
to Figure 6. The simplest and least expensive method is a
resistor as shown in Figure 6a. The value of the resistor is
determined from the expression
V+
VRX
RX
4–20mA
RX = VCC /40mA – 75Ω
3
15
2
and the full scale voltage drop is
RCV420
14
1
VRX = 20mA x RX.
For a system operating off of a 32V supply RX = 725Ω and
VRX = 14.5V. In applications that cannot tolerate such a
large voltage drop, use circuits 6b or 6c. In circuit 6b a
power JFET and source resistor are used as a current limit.
The 200Ω potentiometer, RX, is adjusted to provide a current
limit of approximately 30mA. This circuit introduces a
1–4V drop at full scale. If only a very small series voltage
drop at full scale can be tolerated, then a 0.032A series 217
fast-acting fuse should be used, as shown in Figure 6c.
VO
a) RX = (V+)/40mA – 75Ω
V+
2N3970
RX
200Ω
4–20mA
3
15
2
For automatic fold-back protection, use the circuit shown in
Figure 15.
RCV420
14
1
VO
b) RX set for 30mA current limit at 25°C.
VOLTAGE REFERENCE
The RCV420 contains a precision 10V reference. Figure 8
shows the circuit for output voltage adjustment. Trimming
the output will change the voltage drift by approximately
0.007ppm/°C per mV of trimmed voltage. Any mismatch in
TCR between the two sides of the potentiometer will also
affect drift, but the effect is divided by approximately 5. The
trim range of the voltage reference using this method is
typically ±400mV. The voltage reference trim can be used to
trim offset errors at the output of the RCV420. There is an
8:1 voltage attenuation from Ref In to Rcv Out, and thus the
trim range at the output of the receiver is typically ±50mV.
V+
f1
4–20mA
3
15
2
RCV420
1
14
VO
c) f1 is 0.032A, Lifflefuse Series 217 fast-acting fuse.
Request Application Bulletin AB-014 for details of a
more complete protection circuit.
The high-frequency noise (to 1MHz) of the voltage reference is typically 1mVp-p. When the voltage reference is
used for level shifting, its noise contribution at the output of
the receiver is typically 125µVp-p due to the 8:1 attenuation
from Ref In to Rcv Out. The reference noise can be reduced
by connecting an external capacitor between the Noise
Reduction pin and ground. For example, 0.1µF capacitor
reduces the high-frequency noise to about 200µVp-p at the
output of the reference and about 25µVp-p at the output of
the receiver.
FIGURE 6. Protecting the Sense Resistors.
–In
1
15
CT
+In
2
14
RCV420
VO
11
3
10
8
V REF
20kΩ
±400mV adjustment at output of reference, and ±50mV
adjustment at output of receiver if reference is used for
level shifting.
FIGURE 7. Optional Voltage Reference External Trim Circuit.
®
7
RCV420
12
VLIN
13
4
+
VIN
3
1N4148
14
IR2
+12V
11
VREG
10
V+
1µF
RG
B 9
RG
402Ω
RLIN1
5760Ω
1
IR1
Q1
XTR105
0.01µF
16
–
VIN
RZ
137Ω
RTD
2
7
VO = 0 to 5V
14
13
5
4
IO = 4mA – 20mA
6
12
RCV420
IRET
Pt100
100°C to
600°C
11
15
IO
2
10
3
E 8
RG
1µF
–12V
RCM = 1kΩ
NOTE: A two-wire RTD connection is shown. For remotely
located RTDs, a three-wire RTD conection is recommended.
RG becomes 383Ω, RLIN2 is 8060Ω. See Figure 3 and
Table I.
0.01µF
FIGURE 8. RCV420 Used in Conjunction with XTR101 to Form a Complete Solution for 4-20mA Loop.
12
RLIN2
RLIN1
13
4
VLIN
+
VIN
1
IR1
1N4148
14
11
IR2
10
VREG
V+
0
RG
RG
1µF
XTR105
3
+15V
1µF
B
E
RG
9
Q1
–15V
0.01µF
16
–
2 VIN
IRET
6
11
12
2
7
IO = 4mA – 20mA
14
13
4
V+
1
15
RCV420
IO
RZ
10
3
8
Isolated Power
from PWS740
9
15
ISO122
5
10
7
8
VO
0 – 5V
2
16
RTD
NOTE: A three-wire RTD connection is shown.
For a two-wire RTD connection eliminate RLIN2.
RCM = 1kΩ
0.01µF
FIGURE 9. Isolated 4-20mA Instrument Loop (RTD shown).
®
RCV420
8
V–
10
4–20mA
+In
3
11
3
15
12
CT
–In
15
RS
2
RS
1
2
VO
(0–5V)
14
RCV420
(1)
CT
14
RCV420
VO
(5–0V)
11
1
10
13
5
+10V
13
4–20mA
5
12
12kΩ
+6.25V
+6.25V
OPA237
20kΩ
10
+In
RG(1)
11
3
12
CT
2
–In
1
RS
15
RCV420
(N)
RS
VO = 6.25V – (0.3125) (IIN)
VO
(0–5V)
14
FIGURE 12. 4-20mA to 5-0V Conversion.
13
5
RCM(1)
IL
NOTE: (1) RCM and RG are used to provide a first order correction of CMR
and Gain Error, respectively. Table 1 gives typical resistor values for RCM
and RG when as many as three RCV420s are stacked. Table II gives
typical CMR and Gain Error with no correction. Further improvement in
CMR and Gain Error can be achieved using a 500kΩ potentiometer for
RCM and a 100Ω potentiometer for RG.
RCV420
RCM (kΩ)
1
2
3
200
67
Load
RX(1)
3
CT
2
+In
RG (Ω)
∞
+In
0
7
23
15
RS
RX(1)
1
14
RCV420
RS
VO
(0-5V)
13
12
5
Power
Supply
–40V (max)
TABLE 1. Typical Values for RCM and RG.
RCV420
CMR (dB)
GAIN ERROR %
1
2
3
94
68
62
0.025
0.075
0.200
+40V (max)
Power
Supply
+In
CT
TABLE II. Typical CMR and Gain Error
Without Correction.
(1)
RX
–In
RX(1)
15
RS
RCV420
RS
14
VO
(0-5V)
13
12
Load
FIGURE 10. Series 4-20mA Receivers.
5
IL
NOTE: (1) RX = RS/
I1
I2
+In
3
CT
2
–In
1
FIGURE 13. Power Supply Current Monitor Circuit.
15
RS
14
RCV420
RS
IL MAX
(16mA –1 )
VO
13
12
5
VO = 0.3125 (I1 – I2)
Max Gain Error = 0.1% (RCV420BG)
FIGURE 11. Differential Current-to-Voltage Converter.
®
9
RCV420
+15V
–15V
4
16
RCV420
99kΩ
300kΩ
1
92kΩ
12
15
75Ω
11.5kΩ
2
VOUT
0–5V
14
10.0V
10
75Ω
1.01kΩ
10.0V
Reference
11
1.27kΩ
3
300kΩ
100kΩ
+5V
13
5
10kΩ
+15V
8
4
8
1MΩ
10kΩ
AT&T
LH1191
Solid-State
Relay
10kΩ
2
7
555
Timer
6
10kΩ
1µF
6.95V
LM193
0.01µF
3
10kΩ
5
1
0.57V
470Ω
4–20mA
Input
47kΩ
22.9kΩ
604Ω
4
2N3904
1µF
Overrange
Output
Underrange
Output
See Application Bulletin AB-014 for more details.
FIGURE 14. 4-20mA Current Loop Receiver with Input Overload Protection.
+15V
–15V
16
4
RCV420
1
300kΩ
75Ω
301Ω
12
99kΩ
92kΩ
15
11.5kΩ
2
0-20mA
Input
14
10
301Ω
1.01kΩ
75Ω
10.0V
Ref
3
300kΩ
11
100kΩ
13
See Application Bulletin AB-018 for more details.
FIGURE 15. 0-20mA/0-5V Receiver Using RCV420.
®
RCV420
10
5
VO
0-5V
PACKAGE OPTION ADDENDUM
www.ti.com
4-Jun-2009
PACKAGING INFORMATION
Orderable Device
Status (1)
Package
Type
Package
Drawing
Pins Package Eco Plan (2)
Qty
RCV420JP
ACTIVE
PDIP
N
16
25
Green (RoHS &
no Sb/Br)
CU NIPDAU
N / A for Pkg Type
RCV420JPG4
ACTIVE
PDIP
N
16
25
Green (RoHS &
no Sb/Br)
CU NIPDAU
N / A for Pkg Type
RCV420KP
ACTIVE
PDIP
N
16
25
Green (RoHS &
no Sb/Br)
CU NIPDAU
N / A for Pkg Type
RCV420KPG4
ACTIVE
PDIP
N
16
25
Green (RoHS &
no Sb/Br)
CU NIPDAU
N / A for Pkg Type
Lead/Ball Finish
MSL Peak Temp (3)
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in
a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check
http://www.ti.com/productcontent for the latest availability information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements
for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered
at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and
package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS
compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame
retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder
temperature.
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Addendum-Page 1
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