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PIERS Proceedings, Kuala Lumpur, MALAYSIA, March 27–30, 2012 1212 Design of ARC Filters by Leap-Frog Method L. Fröhlich, J. Sedláček, and M. Friedl Brno, FEEC BUT, UTEE, Kolejni 2906/4, Brno 612 00, Czech Republic Abstract— The sphere concerning frequency filters is constantly developing and there are many principles of non-cascade realizations which can be used for the design of ARC filters. Unfortunately, due to a very difficult design of the certain types of filter synthesis methods these filter realizations are not properly described and there is no detailed description of their usage in practice. One of these realizations is the Leap-Frog filter synthesis method. The article describes the method of the filter design of ARC filters growing from the connection of the RLC filters. This method of the design is not used very often due to fact of a very difficult design and bigger amount of active elements (OAs). But on the other hand, this method exhibits considerable advantages as very small filter sensitivity and excellent dynamic qualities. Thus, it is ideal by filter realizations with area of switching capacitors and their following usage in integrated circuits. The aim of contribution will be following — from the created complete analysis of filters realizing LP, HP, BP, BR, LPN and HPN filters with either configurations T or Π prescribe their filter design and create a suitable description for their optimal using. Some circuits will be realized physically for the evaluation of the filter design method as well as frequency usage of designed filters by using of modern active elements (OAs). 1. INTRODUCTION The Leap-Frog method of filter synthesis is leading to non-cascade filter block connections. Circuit structure of ARC filters created with the help of Leap-Frog combines the method of cascade block realization and realization growing from ladder RLC filters. The principle of realization is based on the transfer of qualities of impedance coupled elements of ladder RLC filters to equivalently reacting connection with impedance distinguished ARC blocks of 1st order or 2nd order. The transformation on the resulting ARC circuit is realized according voltage and current ratio of the ladder RLC filter. These ratios are simulated by dyad of voltage relations. Integral or differential relations between current and voltage on inductors or capacitors are simulated by integrators which can be made by OA with capacitor in feedback [1]. If we want to design a circuit with the help of this method, there are several possibilities. The easiest one may be the use of description of original RLC circuit with the help of signal flow graph and their following transfer to the block structure with integrators. The easiest structures with integrators are defined crosswise connected capacitor or lengthwise connected inductor. Conversely, the most difficult structures are defined with crosswise connected of parallel combination or crosswise series of combination of inductor or capacitor. 2. THE SYNTHESIS OF LEAP-FROG FILTERS For defining of complete design and detecting individual qualities and parameters it is enough to design ARC circuits for the lowest possible order of filter. Thus for LP and HP it is suitable to realize 2nd and 3rd order and for BP and BR of 4th and 6th order for the filter configuration in form Π and T . With the help of these designs it is obvious in which situations it is necessary to add other summation of current to the circuit, with what number of OA we have to count, detection of dynamic qualities or spread of building elements, sensitivity. As an example for this article can be presented filter design of 3rd order LP filter in T configuration for input parameters FM = 10 kHz, FP = 15 kHz, KZV L = −3 dB a KP OT = −15 dB with Tchebyshev approximation. In the Fig. 1, there is a connection of RLC filter with the division of elements for creating of formulas. For creation of signal flow graph we have to set circuit formulas for individual elements, see (1), (2), (3), (4) and (5): UR1 U1 − UC2 − UL1 IR1 = = , (1) R1 R1 Progress In Electromagnetics Research Symposium Proceedings, KL, MALAYSIA, March 27–30, 2012 1213 UL1 pL1 IC2 = pC2 UL3 = pL3 UR2 = R2 IL1 = UC2 IL3 IR2 U1 − UR1 − UC2 , pL1 IL1 − IL3 = , pC2 UC2 − U2 = , pL3 U2 = . R2 = (2) (3) (4) (5) According to set of formulas it is not a problem to realize formulation of individual elements of RLC circuit with the help of signal flow graph, see Fig. 2. It is obvious that in signal flow graph some changes are realized with the red color. It was necessary to add other two summations of current between IR1 and −IL1 , IL3 and −IR2 which leads to increase of number of OA in the circuit for two. And also to adjust the formula (2), (3) and (5) due to the polarity of currents and voltage and their connection, multiplying whole formula by the value −1. To reach realization of ARC filters with the help of available integrator it is necessary to transfer current node −IL1 a IL3 to voltage with the help of multiplying of current and voltage chosen 2 /pL )I by regulating rezistor RN . After this modification we get −UIL1 = (RN 1 U L1 . The same modification can be applied also for node IL3 . Final connection of signal flow graph from which we will deduce setting of ARC circuit can be seen in the Fig. 3. rd Figure 2: Scheme of RLC elements with help of signal flow graph. Figure 1: RLC filter of LP of the 3rd order in T configuration. Figure 3: Final scheme of signal flow graph. Rn1 R1 Rn1 Rn2 Rn2 out2 - 3400 a1 = 0,446 1080 / a1 a1 = 0,316 1080 2414 / a2 OUT a1 * 2414 a2 = 2,338 Cl3 10nF 0 0 - 3040 2414 / a2 a2 = 2,511 Cl1 10nF a2 * 960 a2 = 3,16 OUT 960 a1 * 2414 a1 = 0,398 + -6dB 0dB + 1.1k 500 out4 a1 * 5400 2414 / a1 Rn1 out1 R2 1.1k R 10k - 6063 / a2 + - R 10k a2 * 2414 + OUT OUT + 0 R 10k OUT + OUT R1 1.1k Rn1 0 C2 10nF R 10k OUT - 0 0 2414 / a1 + 0 0 a2 * 2414 Rn2 Rn2 1700 5400 out5 out3 6050 1920 Figure 4: ARC filters with integrators and description of possible design of dynamical ratios in the circuit. PIERS Proceedings, Kuala Lumpur, MALAYSIA, March 27–30, 2012 1214 With the help of final signal flow graph it is not problematic to set resulting ARC circuit. In the resulting circuit of ARC filters the realization of the coil is obvious with the help of two OA (amplifier + inverting integrating transfer I-U) and capacitors with the help of one OA (inverting integrating transfer I-U). Thus it is obvious that LP with Π configuration must be much easier. On the one hand, due to realization only on coil of the circuit. But on the other hand also due to unadding additional current summation. As it is in our case, due to series connection of the certain element with loading resistors. Complete scheme of filter is depicted in Fig. 4. The biggest advantage of these connections is the possibility of compensation of scatter of building elements mainly capacitors due to re-counting of original RLC circuit, see Fig. 1. Due to this re-counting so that the value of capacitors C2 = 10 nF and option of the value of capacitors Cl1 a Cl3 to the same value, there is a spread of element value kC = 1 and kR = 10.4. The option of the value kC = 1 is problematic mainly for BP and BR by the T filter configuration by choice the option of approximation with the zero transfer. In ARC connection there are certain modifications of regulation rezistor RN . These modifications are cause by dynamical modifications in the circuit so that maximum transfer on the individual outputs was the most consistent. The principle is realized so that the direct way from input to output is multiplying by constant a1 — decay and after that divided by constant a2 — gain. In the second part we will divide by constant a1 and after that multiple by constant a2 . Thus all maxims will be in acceptable extent and the circuit gains the excellent dynamics. Simulations with the help of the programme PSpice for verification of dynamical ratios in the circuit after a modification, are seen in the Fig. 5. The last modification is defining the whole filter transfer. It is possible to keep whole transfer outgoing from RLC circuit, it means −6 dB or lengthwise resistor R1 or multiple constant K according to the required whole transfer. 0 10 100 1000 10000 100000 -20 Attenuation [dB] 1000000 LP_T_out1 LP_T_out2 LP_T_out3 LP_T_out4 LP_T_out5 -40 -60 -80 -100 -120 Frequency [Hz] Figure 5: Simulation of dynamical ratios after the modification of transfers on individual outputs of the circuits. 0 100 1000 10000 100000 -5 Attenuation [dB] -10 -15 -20 -25 -30 -35 -40 Frequency [Hz] Figure 6: Sensitivity simulation of ARC filter with real elements. Progress In Electromagnetics Research Symposium Proceedings, KL, MALAYSIA, March 27–30, 2012 1215 Table 1: Overview of the number of OA for filters LP , HP , BP and BR designed by the Leap-Frog method. Order of filter LP Π Number of OA T Order of filter HP Π Number of OA T 2 4 4 2 6 6 Order of filter BP Π Number of OA T Order of filter BP Π Number of OA T 3 4 7 3 8 9 4 7 7 4 11 11 4 7 7 4 9 9 5 7 10 5 13 14 6 9 11 6 12 14 6 10 10 6 16 16 8 13 13 8 17 17 7 10 13 7 18 19 10 15 17 10 20 22 8 13 13 8 21 21 12 19 19 12 25 25 9 13 16 9 23 24 10 16 16 10 26 26 14 21 23 14 28 30 The fact that ARC circuits designed with the help of the methods outgoing from the characteristic of RLC circuit exhibit practically the lowest sensitivity is demonstrated in the Fig. 6. For the comparison of this method with other design methods, it can be also important to consider the number of OA in the circuit, as it is shown in the Table 1. This design method is specific by the highest number of OA. It is necessary to think in advance with which kind of filter configuration we will realize the circuit due to the overall number of OA. For LP and HP it is much suitable to use Π filter configuration or to use T filter configuration in case of even orders of the filter. For BP and BR is much more suitable to use Π filter configuration. 3. CONCLUSION To sum up, it can be said that even despite the difficulty with the design it is possible to design certain circuits with the help of this method. Mainly, this will include LP and BP filters which contain acceptable number of OA, on the contrary with BR or HP filters which have a big number of OAs in the circuit. For the use of LP or BP filters it is supported by the small spread of the building elements and the possibility of design of the capacity values in tolerance orders E6 or E12. Except for this, these circuits represent the smallest sensitivities and excellent dynamical ratios. Due to the overall problematic of these circuits, the circuit program is created for the complete synthesis of these circuits. The program will enable to display of the dynamical ratios in the circuit and the option of the capacitor values for capacitors orders. The program is the advantage for the designer so that they needn’t work out the synthesis for particular input parameters and at the same time they could compare these resulting circuits with filters designed using other methods. ACKNOWLEDGMENT The research described in the paper was financially supported by grant of Czech ministry of industry and trade No. FR-TI1/001, GACR 102/09/0314 and project of the BUT Grant Agency FEKT-S11-15. REFERENCES 1. Sedláek, J. and K. Hájek, “Kmitočtové filtry,” 1. vydánı́, 535, BEN, Technická Literatura, Praha, 2002, ISBN 80-7300-023-7. 2. Dimopoulos, H. G. and A. G. Constantinidis, “Linear transformation active filters,” IEEE Trans. CAS, Vol. 25, No. 10, 845–852, 1978. 3. Ghausi, M. S. and K. R. Laker, Modern Filter Design, Practice Hall, New Persey, 1981. 4. Kapustin, V. I., Aktivnye RC-filtry Vyskovo Porjadka, Radio i svjaz, Moskva, 1985. 5. Sedra, A. and K. Martin, “Design of signal-flow graph (SFG) aktive filters,” IEEE Trans. CAS, Vol. 25, No. 4, 185–195, 1978.