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5.1 Dr. Yuri Panarin, DT021/4, Electronics Introduction Log and Antilog Amplifiers are non-linear circuits in which the output voltage is proportional to the logarithm (or exponent) of the input. It is well known that some processes such as multiplication and division, can be performed by addition and subtraction of logs. They have numerous applications in electronics, such as: 6. Log and AntiLog Amplifiers • • • • 1 FT221/4 Electronics – 6 Log and AntiLog Amplifiers Two basic circuits Multiplication and division, powers and roots Compression and Decompression True RMS detection Process control FT221/4 Electronics – 6 Log and AntiLog Amplifiers 2 Notes There are two basic circuits for logarithmic amplifiers • (a) transdiode and Ri (b) diode connected transistor Ri Q Q vi vi vo vo Most logarithmic amplifiers are based on the inherent logarithmic relationship between the collector current, Ic, and the base-emitter voltage, vbe, in silicon bipolar transistors. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 3 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 4 5.2 Dr. Yuri Panarin, DT021/4, Electronics Transdiode Log Amplifier Notes The input voltage is converted by R1 into a current, which then flows through the transistor's collector modulating the base-emitter voltage according to the input voltage. The opamp forces the collector voltage to that at the noninverting input, 0 V From Ebers-Moll model the collector current is I c = I s (e qVbe / kT − 1) = I s (eVbe / VT − 1) ≈ I s ⋅ eVbe / VT where Is is saturation current, q is the charge of the electron 1.6x10-9 Coulombs, k is the Boltsman’s constant 1.38x10-23 Joules, T is absolute temperature, VT is thermal voltage. I c = I s (e 38.6Vbe − 1) ≈ I s ⋅ e 38.6Vbe For room temperature 300oK The output voltage is therefore i Vout = −Vbe = −VT ln C IS v V = − T lg i 2.3 Ri I S Vin = − 0.0259 ⋅ ln Ri ⋅ Is 5 FT221/4 Electronics – 6 Log and AntiLog Amplifiers Dynamic range of Log Amp. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 6 Notes Test: Discuss the factors limiting the dynamic range of transdiode log amplifier. Suggest the methods to increase dynamic range (a) The output is a perfect log function when IC>>IS. For the small input Voltage (i.e. current) this limits the lower end of the dynamic range. Vbe / V Vbe / V qVbe / kT I c = I s (e − 1) = I s (e I + IS Vout = −Vbe = −VT ln C IS T − 1) ≈ I s ⋅ e I ≈ −VT ln C IS T To extend the lower end of the dynamic range use transistor with small IS., e.g. for LM394 IS =0.25pA FT221/4 Electronics – 6 Log and AntiLog Amplifiers 7 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 8 5.3 Dr. Yuri Panarin, DT021/4, Electronics Dynamic range of Log Amp. Notes (b) At upper end of the dynamic range the limitations is due to the bulk resistance of base and emitter regions – rBE. Therefore Vbe must be corrected to I +I Vbe = VT ln C S + rBE I C IS output error is: actual output – ideal output I (1 + p / 100) I − K ln i OutputError = K ln i IS IS = K ln(1 + p / 100) Typically rBE is in range from 0.25 Ω to 10 Ω To extend the upper end of the dynamic range use transistor with small rBE. e.g. for LM394 rBE =0.5 Ω 9 FT221/4 Electronics – 6 Log and AntiLog Amplifiers Dynamic range of Log Amp. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 10 Notes (c) The second factor is non-idealities of opamp, i.e. input bias current IOS I C + I OS Vout = −VT ln IS and offset voltage VOS. RI + RI OS − VOS V + RI OS − VOS = −VT ln i Vout = −VT ln C RI S RI S this limits the lower end of the dynamic range To extend the lower end of the dynamic range use ultra-low offset opamps or special offset nulling techniques. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 11 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 12 5.4 Dr. Yuri Panarin, DT021/4, Electronics Dynamic range of Log Amp. Notes For LM394 rBE =0.5 Ω, and IS =0.25pA (at room temperature). Estimate the log conformity error at IC=1mA, 100 µA and 10 µA. For IS=1 mA the output error is 0.5Ω x 1mA= 0.5 mV. Therefore 0.5mV = 26mV ln(1 + p / 100) this gives p = (exp( 0.5mV / 26 mV ) − 1) ⋅ 100% ≈ 1.94% Estimate the max dynamic range with-in log conformity 1% outputerror = 26mV ln(1 + 1% / 100%) ≈ 0.26mV The upper limit is IC=0.26mV x /0.5 Ω =0.52 mA The lower limit is 0.25 pA / 1% =25 pA. The dynamic range is 0.52mA/25 pA=0.02 x 109 =2 x 107 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 13 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 14 Notes Thermal and Frequency stability This equation yields the desired logarithmic relationship over a wide range of currents, but is temperature-sensitive because of VT and IS resulting in scale-factor and offset temperature-dependent errors. The system bandwidth is narrower for small signals because emitter resistance increases for small currents. The source impedance of voltage signals applied to the circuit must be small compared to Ri. Omitting Ri yields a current-input log amp. Using a p-n-p transistor changes the polarity of input signals acceptable but limits the logarithmic range because of the degraded performance of p-n-p transistors compared to n-p-n transistors FT221/4 Electronics – 6 Log and AntiLog Amplifiers 15 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 16 5.5 Dr. Yuri Panarin, DT021/4, Electronics IC Log Amps. Notes These basic circuits needs additional components to improve the overall performance, i.e: • • • • • to provide base-emitter junction protection, to reduce temperature effects, bulk resistance error and op amp offset errors, to accept bipolar input voltages or currents, and to ensure frequency stability. Such circuit techniques are used in integrated log amps: AD640, AD641, ICL8048, LOG100, 4127. IC log amps may cost about ten times the components needed to build a discrete-component log amp. Nevertheless, achieving a 1% logarithmic conformity over almost six decades for input currents requires careful design. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 17 Temperature Compensation v vo = −VT ln i R1I S FT221/4 Electronics – 6 Log and AntiLog Amplifiers 18 Notes The equation for output voltage shows that the scale factor of the basic transdiode log amp depends on temperature because of VT and that there is also a temperature-dependent offset because of IS. Temperature compensation must correct both error sources. Figure (next slide) shows the use of a second, matched, transistor for offset compensation and a temperature-dependent gain for gain compensation. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 19 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 20 5.6 Dr. Yuri Panarin, DT021/4, Electronics Temperature Compensation R1 Q1 vi R4 D1 Notes R3 +to Q2 V1 R2 vo Ir v vo = −VT ln i R1 I S 1 Temperature compensation in a transdiode log amp: a second transistor (Q2) compensates the offset current (IS) and a temperature-sensitive resistor (R4) compensates the scale factor VT FT221/4 Electronics – 6 Log and AntiLog Amplifiers 21 22 Notes Temperature Compensation For transistors Q1 & Q2 we have FT221/4 Electronics – 6 Log and AntiLog Amplifiers v I vBE1 = VT ln i vBE 2 = VT ln r R I 1 S1 IS2 where Ir is a reference, temperature-independent, current. The output voltage will be R R R I I R vo = v1 1 + 3 = (vBE 2 − vBE1 )1 + 3 = VT 1 + 3 ln r ⋅ S 1 1 R R 4 R4 I S 2 vi 4 Matched transistors (IS1 = IS2) will cancel offset. In order to compensate the gain dependence on temperature, R4 must be much smaller than R3 and such that d(VT/R4)/dT = 0. This requires dR4/R4 = dVT/VT (= l/T). At T = 298 K, the temperature coefficient of R4 must be 3390 x 10-6K. D1 protects the base-emitter junction from excessive reverse voltages. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 23 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 24 5.7 Dr. Yuri Panarin, DT021/4, Electronics Notes Stability Considerations Transdiode circuits have a notorious tendency to oscillate due to the presence of an active element in the feedback that can provide gain rather than loss. Consider the voltage-input transdiode. Ignoring op amp input errors, we have Vn = Vi − R ⋅ I c and Vo = −VBE The feedback factor β for a given value of Vi, R Q is determined as β = dVn / dVo = R ⋅ dI c / dVBE vi Differentiating IC and using the fact that Ic = Vi/R, we obtain β = R ⋅ I c / VT = Vi / VT vo indicating that β can be greater than unity. For instance, with Vi = 10 V we have β = 10/0.026 = 400 = 52 dB, indicating that in the Bode diagram the |1/β | curve lies 52 dB below the 0 dB axis. Thus, the |1/β| curve intersects the |a| curve at fc >> ft, where the phase shift due to higher-order poles is likely to render the circuit unstable; an additional source of instability is the input stray capacitance Cn FT221/4 Electronics – 6 Log and AntiLog Amplifiers 25 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 26 Notes Range Considerations The transdiode circuit is compensated by means of an emitter resistor RE to decrease the value of β and a feedback capacitor CF to combat Cn, as shown. To investigate its stability, refer to the incremental model, where the BJT has been replaced by its common-base small-signal model. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 27 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 28 5.8 Dr. Yuri Panarin, DT021/4, Electronics Range Considerations Notes Transistor parameters re and ro depend on the operating current Ic, re = αVT / I C ≈ VT / I C ro = V A / I C where VA is called the Early voltage (typically ~ 100 V). Cµ is the basecollector junction capacitance. Both Cµ and Cn are typically ~10 pF range. R1 = R || ro || (rd + R ) and R 2 = re + RE KCL at the summing junction yields Eliminating ie and rearranging yields vn (1 / R1 + jω (Cn + C µ ) ) + α ⋅ ie + jωC F (vn + vo ) vn 1 + jωR1C1 1 + jωR 2C F = vo R1 R2 where ie=-vo/R2 and C1=Cn+Cµ+CF 1 vo R 2 1 + jωR 2C F ≡ = β vn R1 1 + jωR1C1 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 29 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 30 Notes Range Considerations 1 vo R 2 1 + j ( f / f z ) 1 1 where f z = and f p = = = ⋅ β vn R1 1 + j ( f / f p ) 2πR1C1 2πR 2C F The | 1/b| curve has a low-frequency asymptote at R2/R1, a high-frequency asymptote at C1/CF, and two breakpoints at f=fz and f= fp. While C1/CF and fz are constant, R2/R1 and fp depend on the operating current IC. As such, they can vary over a wide range of values. The hardest condition is when Ic = Ic(max), since this minimizes the value of R2/R1 while maximizing that of fp,. As a rule of thumb, RE is chosen to make R2(min)/R1 ~ 0.5 for a reasonably low value of |β |max, CF is chosen to make fp(max) ~ 0.5 fc for reasonable phase margin. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 31 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 32 5.9 Dr. Yuri Panarin, DT021/4, Electronics Speed of Response Notes As the input level is decreased, we witness an increasing dominance of fp , which slows down the dynamics of the circuit. Since at sufficiently low current levels re>>RE, we have fp=1/(2πreCF) The corresponding time constant is τ = reCF=(VT/IC)CF =(VT/ Vi)RCF indicating that τ is inversely proportional to the input level, as expected. For instance, with Ic = 1 nA and Cp = 100 pF, we have τ = (26 x 10-3/10-9) x 100 x 10-12 = 2.6 ms. It takes 4.6 τ for an exponential transition to come within 1 percent of its final value, therefore our circuit will take about 12 ms to stabilize to within 1 percent. This limitation must be kept in mind when operating near the low end of the dynamic range. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 33 Diode-connected Log Amp FT221/4 Electronics – 6 Log and AntiLog Amplifiers 34 Notes In the second circuit a BJT connected as a diode to achieve the logarithmic characteristic. The analysis is the same as above for the transdiode connection, but the logarithmic range is limited to four or five decades because the base current adds to the collector current. On the pro side, • the circuit polarity can be easily changed by reversing the transistor, • the stability improves, and • the response is faster. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 35 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 36 5.10 Dr. Yuri Panarin, DT021/4, Electronics Notes Input Current Inversion The basic log amp in only accepts positive input voltages or currents. Negative voltages or currents can be first rectified and then applied to the log amp, but this adds the errors from the rectifier. Alternatively, the log amp can be preceded by a precision current inverter. The current inverter in Figure below uses two matched n-p-n transistors and a precision op amp to achieve accurate current inversion. The collector-base voltage in both Q1 and Q2 is 0 V, so that the Ebers-Moll model for BJT transistors leads to ie1 = I ES 1 (e vBE 1 / VT − 1) ie 2 = I ES 2 (e vBE 2 / VT − 1) where IES1 and IES2 are the respective emitter saturation currents of Q1 and Q2. 37 FT221/4 Electronics – 6 Log and AntiLog Amplifiers FT221/4 Electronics – 6 Log and AntiLog Amplifiers 38 Notes Input Current Inversion From circuit inspection, assuming an op amp with infinite open-loop gain but finite input currents and offset voltage, ie1 = ii + I b1 io = ii = v BE1 + Vio ie 2 = io + I b 2 Solving for the output current in terms of the input current yields v BE 2 I I ES 2 Vio / VT + I ES 2 1 + b1 eVio / VT − I ES 2 − I b 2 e I I ES 1 ES 1 which shows that, in order to have small gain and offset errors, the offset voltage must be small compared to VT, the op amp offset current must be small compared to the input current, and Q1 and Q2 must be matched. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 39 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 40 5.11 Dr. Yuri Panarin, DT021/4, Electronics Exponential Amplifiers Notes An exponential or antilogarithmic amplifier (antilog amp), performs the function inverse to that of log amps: its output voltage is proportional to a base (10, e) elevated to the ratio between two voltages. Antilog amps are used together with log amps to perform analog computation. Similar to Log Apms there are two basic circuits for logarithmic amplifiers • (a) transdiode and • (b) diode connected transistor FT221/4 Electronics – 6 Log and AntiLog Amplifiers 41 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 42 Notes Antilog Amplifier Interchanging the position of resistor and transistor in a log amp yields a basic antilog amp. The base-collector voltage is kept at 0 V, so that collector current is given by ic ≈ I s ⋅ exp(v BE / VT ) vo = iC R1 = I S R1 exp(−vi / VT ) and for negative input voltages we have: There is again a double temperature dependence because of IS and VT. Temperature compensation can be achieved by the same technique shown for log amps. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 43 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 44 5.12 Dr. Yuri Panarin, DT021/4, Electronics Notes Temperature Compensation The input voltage is applied to a voltage divider that includes a temperature sensor. If R3 ic1 ≈ I s1 exp(vBE / VT ) = Vr / R5 » R4, vBC1 ~ 0V and applying to Q1 yields I c = I s (exp(vBE / VT ) − 1) where Vr is a reference voltage and we have assumed VBE1>>VT (25 mV). In Q2 VBC2 = 0V and hence : ic 2 ≈ I s 2 exp( vBE 2 / VT ) = Vo / R 5 Also: R4 vi = vBE1 − vBE 2 R 4 + R3 Substituting vBE1 and vBE2, and solving for vo, if Ql and Q2 are matched yields v R1 R4 vo ≈ Vr exp( − i ) R5 VT R3 + R 4 Therefore, if the temperature coefficient of R4 is such that dR4/R4 = dVT/VT = l/T the voltage divider will compensate for the temperature dependence of VT. At T = 298 K, the temperature coefficient of R4 must be 3390 x 10-6K. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 45 Log-Antilog FT221/4 Electronics – 6 Log and AntiLog Amplifiers 46 Notes Log and antilog amp circuits include the same elements but arranged in different feedback configurations. Some integrated log amps have uncommitted elements allowing us to implement antilog amps. Some IC (like ICL8049) are a committed only antilog amp. Some so-called multifunction converters (AD538, LH0094, 4302) include op amps and transistors to simultaneously implement log and antilog functions, or functions derived thereof, such as • • • • multiplication, division, raising to a power, or taking a root FT221/4 Electronics – 6 Log and AntiLog Amplifiers 47 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 48 5.13 Dr. Yuri Panarin, DT021/4, Electronics Notes Basic Multiplier Multipliers are based on the fundamental logarithmic relationship that states that the product of two terms equals the sum of the logarithms of each term. This relationship is shown in the following formula: ln(a x b) = ln a + ln b This formula shows that two signal voltages are effectively multiplied if the logarithms of the signal voltages are added. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 49 Multiplication Stages FT221/4 Electronics – 6 Log and AntiLog Amplifiers 50 Notes The multiplication procedure take three steps: 1. 1. To get the logarithm of a signal voltage use a Log amplifier. V1 = ln(V1 ) and V2 = ln(V2 ) * * 2. 2. By summing the outputs of two log amplifiers, you get the logarithm of the product of the two original input voltages. VO* = V2* + V2* = ln(V1 ) + ln(V2 ) = ln(V1 ⋅V2 ) 3. 3. Then, by taking the antilogarithm, you get the product of the two input voltages as indicated in the following equations: VO = exp(VO* ) = exp[ln(V1 ⋅V 2) ] = V1 ⋅ V2 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 51 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 52 5.14 Dr. Yuri Panarin, DT021/4, Electronics block diagram of an analog multiplier Notes The block diagram shows how the functions are connected to multiply two input voltages. Constant terms are omitted for simplicity. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 53 Basic Multiplier Circuitry FT221/4 Electronics – 6 Log and AntiLog Amplifiers 54 Notes The outputs of the log amplifier are stated as follows: V Vout (log1) = − K1 ⋅ ln in1 K2 V Vout (log 2) = − K1 ⋅ ln in 2 K2 where K1 = 0.025 V, K2 = R⋅Iebo and R = R1 = R2= R6. The two output voltages from the log amplifiers are added and inverted by the unity-gain summing amplifier to produce the following result: V V Vout ( sum ) = K1 ⋅ ln in1 + ln in 2 = K 2 K2 Vin1 ⋅ Vin 2 = K1 ⋅ ln 2 K2 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 55 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 56 5.15 Dr. Yuri Panarin, DT021/4, Electronics Notes This expression is then applied to the antilog amplifier; the expression for the multiplier output voltage is as follows: 1 Vout ( sum ) V ⋅ V = − K 2 ⋅ exp K1 ⋅ ln in1 2 in 2 = Vout (exp) = − K 2 ⋅ exp K K 1 1 K 2 V ⋅V V ⋅V = − K 2 in1 2 in 2 = − in1 in 2 K2 K2 The output of the antilog (exp) amplifier is a constant (1/K2) times the product of the input voltages. The final output is developed by an inverting amplifier with a voltage gain of — K2. V ⋅V Vout = − K 2 − in1 in 2 = Vin1 ⋅ Vin 2 K2 57 FT221/4 Electronics – 6 Log and AntiLog Amplifiers Four-Quadrant Multipliers FT221/4 Electronics – 6 Log and AntiLog Amplifiers 58 Notes Four-Quadrant Multiplier is a device with two inputs and one output. V1 Vout Vout = k ⋅ V1 ⋅ V2 V2 Typically k = 0.1 to reduce the possibility of output overload. It is called four-quadrant since inputs and output can be positive or negative. An example device is Motorola MC1494, powered by ± 15 V power supply FT221/4 Electronics – 6 Log and AntiLog Amplifiers 59 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 60 5.16 Dr. Yuri Panarin, DT021/4, Electronics Multiplier Applications Notes Alongside the multiplication Multipliers have many uses such as: • • • • • Squaring Dividing Modulation / demodulation Frequency and amplitude modulation Automatic gain control 61 FT221/4 Electronics – 6 Log and AntiLog Amplifiers FT221/4 Electronics – 6 Log and AntiLog Amplifiers 62 Notes AM & Squaring Amplitude Modulation VLF Vout VRF Squaring circuit Vin Vout FT221/4 Electronics – 6 Log and AntiLog Amplifiers 63 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 64 5.17 Dr. Yuri Panarin, DT021/4, Electronics Notes Divider by feedback Divider Vm = K ⋅ Vx ⋅ Vout i1 = Vin R1 i2 = Vm R2 Vin = −Vm = − K ⋅ Vx ⋅Vout Vout = Vm Vin =− K ⋅ Vx K ⋅ Vx Square root: If Vx = Vout Vout = − Vin K ⋅ Vout Vout = − Vin K FT221/4 Electronics – 6 Log and AntiLog Amplifiers 65 Test problems Sketch the diagram for transdiode log amplifier and define its gain. Describe the stability problem of this circuit. Suggest the model to improve stability range. Use the BJT common –base small-signal model shown on the Figure. 4. In this circuit let R=10 kΩ, 1 mV < Vi < 10 V, Cµ + Cn = 20 pF, VA = 100 V, rd = 2 MΩ, and f1= 1 MHz. Find suitable values for Cf and RE. For this circuit, find the time needed for output voltage to come within 1 % of its final value (in worst case). Discuss the factors limiting the dynamic range of transdiode log amplifier. Suggest the methods to increase dynamic range For LM394 rs ==0.5 Ω, and IS =0.25pA (at room temperature). Estimate the log conformity error at IC=1mA, 100 µA and 10 µA. Estimate the max dynamic range with-in log conformity 1% 6. 7. 8. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 66 Notes 1. 2. 3. 5. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 67 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 68 5.18 Dr. Yuri Panarin, DT021/4, Electronics Notes Transistor parameters re and ro depend on the operating current Ic, ro = V A / I C re = αVT / I C ≈ VT / I C where VA is called the Early voltage (typically ~ 100 V). Cµ is the basecollector junction capacitance. Both Cµ and Cn are typically ~10 pF range. R1 = R || ro || (rd + R ) and R 2 = re + RE KCL at the summing junction yields Eliminating ie and rearranging yields vn (1 / R1 + jω (Cn + C µ ) ) + α ⋅ ie + jωC F (vn + vo ) vn 1 + jωR1C1 1 + jωR 2C F = vo R1 R2 where ie=-vo/R2 and C1=Cn+Cµ+CF 1 vo R 2 1 + jωR 2C F ≡ = β vn R1 1 + jωR1C1 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 69 Analogue Multipliers FT221/4 Electronics – 6 Log and AntiLog Amplifiers 70 Notes In analog-signal processing the need often arises for a circuit that takes two analog inputs and produces an output proportional to their product. Such circuits are termed analog multipliers. There are two different approaches to analog multipliers One of them is based on log/antilog amplifiers Another utilizes the exponential transfer function of bipolar transistors (Gilbert cell) . In following sections we consider applications of IC multipliers based on log/antilog amplifiers FT221/4 Electronics – 6 Log and AntiLog Amplifiers 71 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 72 5.19 Dr. Yuri Panarin, DT021/4, Electronics Notes Log/Antilog Converter The log and antilog functions can be combined in slide rule fashion to perform such operations as • multiplication, • division, • exponentiation, and • root computation. With the help of simple op amp circuitry it can be configured for additional operations, such as • multifunction conversion and • non-integer exponent approximations, • coordinate conversion, and • true rms-to-dc conversion. Although now the tendency is to implement these functions digitally, considerations of cost and speed often require their implementation in analog hardware. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 73 Multifunction Converters FT221/4 Electronics – 6 Log and AntiLog Amplifiers 74 Notes A multifunction converter (4302) is a circuit that accepts three inputs, Vx, Vy, and Vz and yields an output Vo of the type: m Vo = KV y Vz Vx where K is a suitable scale factor (typically K = 1), and m is a user-programmable exponent, in the range 0.2 < m < 5 where K is a suitable scale factor (typically K = 1), and m is a userprogrammable exponent, in the range 0.2 < m < 5 By proper selection of input configuration and exponent, the circuit can be programmed for a variety of operations: Vo = VxV y , Vx / Vz , Vzm , n Vz , 1 / Vx etc. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 75 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 76 5.20 Dr. Yuri Panarin, DT021/4, Electronics Notes 4302 block diagram The circuit diagram of 4302 is shown with frequency compensation and reversepolarity protection omitted for simplicity. Vy V V By op amp action, we have V I z = z Io = o Ix = x I y = Rz Ro Ry Rx The voltages at pins 6 and 12 are proportional to the log ratios of the corresponding currents: I V6 = VT ln z Ix I V12 = VT ln o Iy FT221/4 Electronics – 6 Log and AntiLog Amplifiers 77 m=1 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 78 Notes 1. V6 and V12 are derived directly from V11 so that V6 = V12 = V11 . By V6 = VT ln (I z / I x ) = V12 = VT ln (I o / I y ) this implies Iz/Ix = Io/Iy that is, Vz/Vx = Vo/Vy. Thus, V Vo = V y z Vx FT221/4 Electronics – 6 Log and AntiLog Amplifiers 79 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 80 5.21 Dr. Yuri Panarin, DT021/4, Electronics Notes m<1 and m>1 2. m < 1: V6 is derived directly from V11 while V12 is derived from V11 via a voltage divider, V12=mV11, where m=R2/(R1+R2). Letting V12=mV6 yields , ln(I o / I y ) = m ln( I z / I x ) = ln( I z / I x ) m that is, (Io / I y ) = (I z / I x )m This, in turn, yields , (Vo / Vy ) = (Vz / Vx ) m that is, m V R2 Vo = V y z , where m = <1 R1 + R 2 Vx 3. m > 1: V12 is derived directly from V11 while V6 is derived from V11 via a voltage divider, V6=(1/m)V11, where (1/m)=R2/(R1+R2). Letting V6=V12/m yields m V R1 + R 2 Vo = V y z , where m = >1 R2 V x FT221/4 Electronics – 6 Log and AntiLog Amplifiers 81 Multiplication and Division FT221/4 Electronics – 6 Log and AntiLog Amplifiers FT221/4 Electronics – 6 Log and AntiLog Amplifiers 82 Notes 83 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 84 5.22 Dr. Yuri Panarin, DT021/4, Electronics Exponentiator - Root Extractor FT221/4 Electronics – 6 Log and AntiLog Amplifiers Notes 85 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 86 Notes 4302 Adjustment In each configuration the scale factor is calibrated by setting the input(s) to 10 V and adjusting Ry for Vo = 10 V. To maintain the accuracy of division at low signal levels, the input offset errors of the X and Z op amps must be nulled as follows 1. With Vz = Vx = 10.0 V, adjust R1 for Vo = 10.0 V. 2. With Vz = Vx = 100 mV, adjust R2 for Vo = 10.0 V. 3. With Vx = 100 mV and Vz = 10.0 mV, adjust R3 for Vo 1.00 V. Repeat the procedure, if necessary. The 4302 provides the following accuracies: • multiply, ±0.25 percent; • divide, ±0.25 percent; • square, ±0.03 percent; • square root, ±0.07 percent. FT221/4 Electronics – 6 Log and AntiLog Amplifiers 87 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 88 5.23 Dr. Yuri Panarin, DT021/4, Electronics Notes Test (2004 Suppl.) The circuit diagram of 4302 is shown in Fig.2 with frequency compensation and reversepolarity protection omitted for simplicity. Assume that RX = RY = RZ = RO. The pins 6, 11, 12 are connected as follows where R1=R2= 15 kΩ. Find the expression for Output Voltage VO. [13 marks] (c) Make appropriate changes/connections to produce expression for Output Voltage [5 marks] V = 5⋅ 3 V /V o 1 2 RY VY iY QY QO iO RO 13 AY VX 1 VZ 7 RX iX RZ iZ AO QZ 2 VO QX AY AO 6 11 12 89 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 4302 Test V Vo = V y z Vx Vo = 5 ⋅ 3 V1 / V2 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 90 Notes m 1. m=1/3, pins 6 and 11 are short circuit, pin 12 – volt. divider 2. m=R2/(R1+R2)=1/3, 3 R2=R1+R2, R1=2 R2 3. 4. 5. 6. V1 is connected to pin VZ V2 is connected to pin VX pin VY is connected to +5 V R3=2R4 is voltage divider for +5V +15V 15V 14 VY 13 Vx 1 VZ 7 -15V 10 3 2 4302 Vo R3 6 +5V 11 12 R4 R1 FT221/4 Electronics – 6 Log and AntiLog Amplifiers R2 91 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 92 5.24 Dr. Yuri Panarin, DT021/4, Electronics 4302 Test 4302 Test V Vo = V y z Vx Vo = 16 ⋅V1 / V 24 m 15V -15V 14 VY V Vo = V y z Vx Vo = 2 ⋅V1 / V2 10 15V 3 13 VY Vx 1 VZ 7 VZ 7 6 93 12 94 4302 Test V Vo = V y z Vx m 14 V Vo = V y z Vx Vo = V13 /V22 15V VY 11 Vo FT221/4 Electronics – 6 Log and AntiLog Amplifiers 4302 Test Vo = 2 ⋅V1 V2 2 12 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 3 4302 1 11 10 13 Vo Vx 6 -15V 14 2 4302 m -15V 10 15V 3 13 14 2 4302 VY 13 1 Vx 1 VZ 7 VZ 7 FT221/4 Electronics – 6 Log and AntiLog Amplifiers 11 12 FT221/4 Electronics – 6 Log and AntiLog Amplifiers http://www.electronics.dit.ie/staff/ypanarin/DT021-notes.htm 3 2 6 95 -15V 10 4302 Vo Vx 6 m 11 Vo 12 96