Download LVPECL terminations - A circuit approach

LVPECL terminations - A circuit approach
Phillip Wissell - February 03, 2014
Introduction
LVPECL is an established high-frequency differential signaling standard that dates back to the 1970s
and earlier when high-speed IC technology was limited to NPN transistors only. Since only an active
pull up could be implemented, external components are required to pull down the output passively.
For DC-coupled LVPECL, these external components both bias the output driver into conduction and
terminate the associated differential transmission line. However, the considerable circuit design
flexibility available for achieving these two requirements when completing the output stage design
can be a source of confusion for first time LVPECL users. They are often confronted with an array of
termination options and no basis upon which to make a selection.
This article approaches the topology and selection of component values in a systematic manner,
beginning with the structure of the output driver and the standard VCC-2V bias and termination
network. The characteristics and limitations of this termination are discussed in depth, and alternate
T and PI terminations, which use fewer components and less power, are introduced and
characterized. Additionally, the use of clock receivers with internal terminations and selection of
bias resistors and coupling capacitors for AC terminations is covered.
The LVPECL Driver
A simplified LVPECL gate is typically implemented with an open emitter driver, as shown in Figure
1.
Figure 1: Equivalent Schematic of an Open Emitter LVPECL driver.
Three things can immediately be noted in Figure 1:
1. The output transistors are not turned on; therefore the driver will not produce an output.
a. In order for Q and nQ to switch, each must be loaded with a dc path to ground.
b. If the output is not to be used the Q and nQ pins can be floated to ensure the outputs are
turned off, minimizing power and reducing noise.
2. The emitter currents of Q and nQ are determined by the selection of external pull down resistors.
Different values for these resistors adjust for different VCCO voltages, power dissipation and p-p
signal swing.
3. VCCO = VCC; Unlike LVCMOS, VCCO cannot be less than VCC to accommodate clock receivers
using different supply voltages. As an example, VCC = 3.3V and VCCO = 2.5V will cause the
output transistors to saturate, drastically reducing switching time.
Differential-output LVPECL drivers are capable of operating at gigahertz frequencies, which
requires that the associated LVPECL receivers are connected to the drivers through properly
terminated transmission lines. Circuit designers can select terminations based on ease of component
placement and power vs. performance tradeoffs, but should always verify signal integrity through
simulations that include trace length and vias.
DC-Coupled LVPECL Terminations
Standard Termination
Shown below in Figure 2 is the standard DC-coupled LVPECL termination.
Figure 2: Standard LVPECL Termination.
Referring to Figure 1, the nominal VTT voltage was set by applying Kirchoff's Voltage Law to the
loop consisting of VCC (=VCCO), R1, Vbe of Q4 and Rterm when Q4 is at the logic low level and its
emitter current is 2mA. VTT is a voltage branch put at the common node of the termination resistors
to both satisfy KVL and ensure that the VTT voltage tracks VCC and VCCO.
The benefit of VTT is that the driver output currents are unaffected by variations in the power supply
voltage. This is particularly important for the logic low transistor; keeping it out of cutoff maintains
the device's switching speed. The clear drawback of this termination scheme is that it requires a -2V
regulator referenced to VCCO.
Thevinin Equivalent Termination
Thevinin Equivalent Termination
In practice the VTT supply is often eliminated with the terminations of Figure 3 shown below, where
both the VTT voltage and the 50-ohm termination resistor for each output are simultaneously
realized by the Thevinin equivalents of two resistor bias strings. The separate terminations for Q and
nQ allow for the option of Q and nQ to be routed separately on uncoupled transmission lines to
different single ended loads.
Figure 3: 3.3V and 2.5V Thevinin Equivalent LVPECL Terminations.
There are five disadvantages of the Thevinin termination:
1. The bias string incurs its own power penalty in addition to the output driver emitter currents,
about 80 mW per output pair on a 3.3V supply.
2. There is no remaining degree of freedom in the termination to accommodate variations in VCCO,
temperature and device processing.
3. A fraction of the variations in VCCO are fed forward to the Thevinin equivalent VTT voltage by the
bias voltage divider; 39% for VCCO=3.3V and 20% for VCCO=2.5V. Therefore control of the
emitter currents, particularly for the logic low output, is not as effective as the standard VTT
termination.
4. For a differential termination, only three resistors are actually required to realize one VTT voltage
and two 50 ohm termination impedances.
5. For each of the Q and nQ signals, the two resistors connected to the clock receiver terminal add
layout complexity and a performance penalty due to additional parasitic capacity over a single
resistor.
PI and T Shunt Terminations
The disadvantages of the Thevinin termination can be either avoided or mitigated by the use of
coupled transmission lines with the PI (aka Delta) or T (aka Y) resistor networks as shown in Figure
4. The common-mode impedance for the PI network is Rbias/2, and for the T network, Zo/2+RTT.
The terminating impedance of the coupled transmission line for the PI network is Zdiff, which equals
2Zo and for the T network, is 2Zo directly. The common mode voltage across RTT has been named
VTT by similarity to VTT = VCC-2.0V.
Figure 4: T and PI LVPECL Termination Networks.
The disadvantages of the Thevinin termination are addressed by these two networks as follows:
1. The power penalty of the Thevinin bias string is eliminated because the termination is powered
directly from the driver currents.
2. The common mode impedance, and therefore negative feedback, can be adjusted to tradeoff
driver current for variations in VCCO, temperature and device processing as shown below in
Table 1.
3. The PI and T networks have better control of the emitter currents through common mode current
feedback. Using as example the T network with RTT = 50 ohms and VCCO = 3.3V, the common
mode feedback from VCCO to the VTT node is 66% (actually somewhat less due to the different
operating points of the output transistors), this is 60% higher than that of the standard
termination feed forward path. While this difference between the two terminations may not seem
significant at first, it is significant when the relatively small voltage drop across the 50 ohm
emitter resistor of the logic low transistor is considered.
4. Only three resistors are required, the minimum necessary to bias the two outputs and terminate
the transmission line. For each network, the Q and nQ transmission lines must be coupled
because each realizes a shunt termination.
5. Only one resistor terminal, and therefore associated parasitic capacity, is placed on each input
terminal of the LVPECL receiver.
Table 1 demonstrates how the PI and T terminations common-mode bias resistors can be adjusted to
accommodate variations in VCCO and device processing. The IDT 853S006 was selected as a
representative device whose LVPECL output is characterized for maximum and minimum logic 0 and
logic 1 voltages across the industrial temperature range. Three cases are calculated: nominal VCCO
voltage, the extreme corner case of -5% VCCO and minimum common mode output voltage over
processing and temperature, and an intermediate case of only -5% VCCO.
Table 1: Output Transistor Currents vs. T and PI Termination Bias Resistors
The minimum bias current for a logic low, desirable for switching speed, is decreased proportionally
to compensate for the increasingly lower probability of the two -5% VCCO cases. The bias resistors
must decrease to accommodate the progressively lower emitter voltages of the output transistors as
more variation in emitter voltages is introduced.
Decreasing the bias resistors also increases the average bias current. Countering this trend is that
decreasing the minimum Ibias, as expected, drops the average bias current. This effect is seen when
comparing the 2.5V VCCO bias currents for the nominal and -5% cases.
The average bias currents for the differential pair are calculated at the VCCO used for each case. In
all cases the bias currents will increase when VCCO is +5%. The designer should select the resistor
value bounded by these cases that best corresponds to the tolerances of their application.
The PI Termination and Coupled Transmission Lines
The PI Termination and Coupled Transmission Lines
When incorporating the PI network of Figure 4 with a coupled transmission line, Zdiff is replaced
with the equivalent impedance of a coupled transmission line terminated in Zdiff. This arrangement
retains the advantages of using Rbias to set the driver Q and nQ bias currents independently and
only one resistor parasitic per receiver terminal. Specific forms of the PI network are shown below
in Figure 5.
Figure 5: 3.3V and 2.5V External PI Terminations.
This termination is most advantageous in board layout when terminating multiple LVPECL signals on
a single package, such as a BGA. In fact this is the same advantage at the receiver as is afforded by
LVDS. The Q and nQ outputs have only one Rbias resistor per transmission line, which makes it easy
to place them on the same side of the PCB as the LVPECL driver, a significant signal integrity
advantage.
In some devices the LVPECL input stage integrates the 50-ohm differential termination resistors
with the common-mode tap brought out to a package pin, typically labeled VT. When implementing
the PI termination, the VT terminal is floated.
The T Termination and Coupled Transmission Lines When incorporating the T network of
Figure 4 with a coupled transmission line, the entire T network is placed at the LVPECL receiver
end of the coupled transmission line. There is only one resistor parasitic per receiver terminal and
the parasitic capacity associated with RTT does not affect differential mode signal integrity as it is
located at the VTT common mode node. The T termination becomes preferred with large fan-out
LVPECL devices, for example a 1:22 fan-out buffer where it may be difficult to fit all the pull-down
bias resistors of the PI termination at the clock driver.
Specific forms of the T network are shown below in Figure 6. For LVPECL devices with integrated
50-ohm differential termination resistors and a common-mode VT tap, the VT pin is pulled to ground
through the external RTT resistor shown in these examples.
Figure 6: 3.3V and 2.5V External T Terminations.
LVPECL Bias for AC-Coupled Terminations
Often LVPECL clock drivers must be AC coupled to a receiver of a different logic family with a
different switching threshold voltage. The LVPECL output must still be dc biased but the use of
blocking capacitors places the requirements to bias the receiver within its common-mode range and
providing the transmission line termination impedance on the LVPECL receiver. The general
external configuration for only the LVPECL driver is shown in Figure 7.
Figure 7: General LVPECL Driver Bias for AC-Coupled Loads.
The values for the Rbias resistors are to be taken from Table 1, which were calculated based on
setting the output transistor emitter current at the switching threshold. The value of Cc is calculated
based on the frequency of the clock and the magnitude of the impedance at the clock frequency.
Coupling capacitor CC selection is based on the amount of parasitic reactance that the cap is
allowed to introduce into the signal path. This maximum impedance is arbitrarily set at 0.2 ohms in
order to calculate Table 2 (shown below) to associate standard cap values and their corresponding
frequency ranges.
Table 2: Standard Coupling Cap values vs. Clock Frequency.
Conclusion
LVPECL is an older technology that dates to when semiconductor processing had not yet matured to
the point where high-performance P-type devices could be fabricated with high-performance N-type
devices. Consequently the role of the P devices had to be handled with external passive elements.
This requirement was exploited in LVPECL as well as the precursor to LVPECL, ECL, by merging the
role of the passive pull-down function with that of a transmission line termination.
Designers often have difficulty designing an appropriate LVPECL termination because the role of the
termination in completing the output stage design is typically never reviewed. The intent of
presenting LVPECL terminations from a circuit perspective is to show how the important factors,
output transistor currents and minimizing component count and power, account for the LVPECL
termination topologies and component values of common terminations. Contemporary
semiconductor processing does produce high-performance P-type devices and the circuit
consequences are the appearance of ground-referenced differential signaling families, such as HCSL
and LVDS. These families eliminate the VTT requirement completely.
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