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Analysis of a simple BJT OpAmp INEL 4202 - Electronics II +15V Q3 v1 QD Q4 Q1 Q2 QE QF Q5 v2 Q6 RA vOUT QC QA RC3 QB RE4 QC -15V Differential-mode analysis Assume β = 100. Apply v1 = +vd /2, v2 = −vd /2. Invoke virtual ground at the emitter of Q1,2 : ic1 ic2 vb5 vb5 vd = gm1 (vd /2) = ic3 = ic4 = gm2 (−vd /2) ⇒ io1 = ib5 = ic4 − ic2 = gm1 (vd /2) − gm1 (−vd /2) = gm1 vd = ib5 (ro2 ∥ro4 ∥Rin,b5 ) = gm1 vd (ro2 ∥ro4 ∥Rin,b5 ) = gm1 (ro2 ∥ro4 ∥Rin,b5 ) For simplicity, let VA = 100V for both pnp and npn transistors, so that ro2 = ro4 = VA . ICQ1 Then ( ) ICQ,1 1 VA vb5 = ∥Rin,b5 vd Vt 2 ICQ1 −gm5 (rOE ∥Rin,b6 ) vc5 = vb5 1 + gm5 RC3 vout ≃ 1 vc5 1 Rin,b5 = rπ,5 + (101)RC3 VA ICQ2 = The design equations are vout ICQ,1 = vd Vt ( 1 VA ∥Rin,b5 2 ICQ1 )( −gm5 (rOE ∥Rin,b6 ) 1 + gm5 RC3 ) vout (vd = 0) = IQ6 RE4 − 15V rπ,6 + rOE Rout = RE4 ∥ 101 Rin = 2rπ,1 = 2rπ,2 Now we can begin assigning values. Select RE4 so that vout (vd = 0) = 0V a large ICQ,6 so that the output stage can drive large loads ICQ,6 = 10mA rπ,6 = RE4 = 15V /10mA = 1.5kΩ 100(0.025V ) = 250Ω 10mA a small ICQ,1 so that Rin is large; Rin = 2 100(0.025) ⇒ ICQ,1 = 10µA ⇒ Rin = 500kΩ ICQ,1 let RC3 = 10kΩ for a large Rin,b5 Rin,b5 = rπ,5 + (101)RC3 ≃ 101(10kΩ) ≃ 1M Ω The gain is ( )( −gm5 (rOE ∥151.5kΩ) 1 + gm5 10kΩ ICQ,5 100V − 0.025V ( ICQ,5 ∥151.5kΩ) ≃ (333.3) ICQ,5 1 + 0.025V 10kΩ vout 10µA ≃ vd 0.025V 1 100V ∥1M Ω 2 10µA ) select ICQ,5 = 50µA; then vout ≃ (333.3) vd ( −281.7 50µA 1 + 0.025V 10kΩ ) = 333.3 × −281.7 = 4471V /V 21 The output resistance is Rout = RE4 ∥ 100V /50µA rπ,6 + rOE ≃ 1.5kΩ∥ = 1.4kΩ 101 101 which is a large value. A second common-collector stage could be added at the output to further reduce this value. Biasing Assume ICB = ICA (same transistor area in QA and QB ) ICB = ICQ,1 + ICQ,2 = 20µA = ICA ≃ 15V − 1.4V ⇒ RA = 680kΩ RA Use an area 5 times larger for (relative to QA ) QC,D,E so that ICQ,5 = 50µA as, desired. Transistor QF will have to be 200 times larger than QD to achieve ICQ,6 = 10mA. The input bias current is ICQ,1/β = ICQ,2/β = 10µA/100 = Ibias = 100nA . Common-mode rejection ratio (CMRR) For our selection for IQB = 20µA, the current source’s Norton resistance for the differential stage is RCS = 100V /20µA = 5M Ω. Using the technique previously shown in the handout for differential amplifiers, vcm vcm = 100 × ≃ vcm/10M Ω rπ,1 + (β + 1)(2RCS ) 250kΩ + 101 × 10M Ω ic1,cm = ic2,cm = β If the active load is assumed perfect (by neglecting the base currents for Q3 and Q4 ) the differential-stage’s output current is zero. If the base currents are taken into account, ic4,cm = β ic1,cm β+2 and the differential-stage’s output current is ( ) β vcm −2 vcm io1,cm = ic4,cm − ic2,cm = −1 = β+2 10M Ω 102 10M Ω Since from this point on, the same loads and gains affect both the differential- and commonmode signals, we can compute the CMRR without actually finding the common-mode voltage gain. io1,dm/v CM RR = | i d /vcm o1,cm |= gm1 (102)10M Ω 10µA = 510M Ω = 204000 = 106dB 2 0.025V