Download AD10465 Dual Channel, 14-Bit, 65 MSPS A/D Converter Data Sheet

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Dual Channel, 14-Bit, 65 MSPS A/D Converter
with Analog Input Signal Conditioning
AD10465
Data Sheet
FEATURES
The AD10465 uses innovative high density circuit design and laser
trimmed, thin film resistor networks to achieve exceptional
matching and performance, while still maintaining excellent
isolation and providing for significant board area savings.
Dual, 65 MSPS minimum sample rate
Channel-to-channel matching, ±0.5% gain error
Channel-to-channel isolation, >90 dB
DC-coupled signal conditioning included
Selectable bipolar input voltage range
(±0.5 V, ±1.0 V, ±2.0 V)
Gain flatness up to 25 MHz: <0.2 dB
80 dB spurious-free dynamic range
Twos complement output format
3.3 V or 5 V CMOS-compatible output levels
1.75 W per channel
Industrial and military grade
The AD10465 operates with ±5.0 V supplies for the analog
signal conditioning with a separate 5.0 V supply for the analogto-digital conversion and 3.3 V digital supply for the output
stage. Each channel is completely independent, allowing
operation with independent encode and analog inputs. The
AD10465 also offers the user a choice of analog input signal
ranges to further minimize additional external signal
conditioning, while remaining general-purpose.
APPLICATIONS
The AD10465 is packaged in a 68-lead ceramic leaded chip
carrier package, footprint-compatible with the earlier
generation AD10242 (12-bit, 40 MSPS) and AD10265 (12-bit,
65 MSPS). Manufacturing is done on the Analog Devices Mil38534 Qualified Manufacturers Line (QML) and components
are available up to Class-H (−40°C to +85°C). The AD6644
internal components are manufactured on Analog Devices’ high
speed complementary bipolar process (XFCB).
Phased array receivers
Communications receivers
FLIR processing
Secure communications
GPS antijamming receivers
Multichannel, multimode receivers
GENERAL DESCRIPTION
PRODUCT HIGHLIGHTS
The AD10465 is a full channel ADC solution with on-module
signal conditioning for improved dynamic performance and
fully matched channel-to-channel performance. The module
includes two wide dynamic range AD6644 ADCs. Each
AD6644 has a dc-coupled amplifier front end including an
AD8037 low distortion, high bandwidth amplifier that provides
high input impedance and gain and drives the AD8138 singleto-differential amplifier. The AD6644s have on-chip track-andhold circuitry and utilize an innovative multipass architecture
to achieve 14-bit, 65 MSPS performance.
1.
Guaranteed sample rate of 65 MSPS.
2.
Input amplitude options, user configurable.
3.
Input signal conditioning included; both channels matched
for gain.
4.
Fully tested/characterized performance.
5.
Footprint-compatible family; 68-lead CLCC package.
FUNCTIONAL BLOCK DIAGRAM
AINA3 AINA2 AINA1
8
7
REF_A
6
AINB3 AINB2 AINB1
3
64
63
62
DRAOUT 12
D0A (LSB) 15
D1A 16
D2A 17
56
REF_B
55
DRBOUT
52
ENCODEB
51
ENCODEB
49
D13B (MSBB)
48
D12B
47
D11B
46
D10B
45
D9B
D3A 18
AD10465
TIMING
D5A 20
D6A 21
D7A 22
11
VREF
DROUT
VREF
DROUT
14
14
D8A 23
TIMING
D10A 25
28
OUTPUT BUFFERING
9
OUTPUT BUFFERING
3
D9A 24
29
31
ENCODEA ENCODEA
32
5
33
34
35
36
D11 D12A D13A (MSBA) D0B (LSBB) D1B D2B
37
38
39
D3B D4B D5B
40
41
D6B D7B
42
D8B
02356-001
D4A 19
Figure 1.
Rev. B
Document Feedback
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
Trademarks and registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700 ©2001–2015 Analog Devices, Inc. All rights reserved.
Technical Support
www.analog.com
AD10465
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Theory of Operation ...................................................................... 12
Applications ....................................................................................... 1
Using the Flexible Input ............................................................ 12
General Description ......................................................................... 1
Applying the AD10465 .................................................................. 13
Product Highlights ........................................................................... 1
Encoding the AD10465 ............................................................. 13
Functional Block Diagram .............................................................. 1
Jitter Considerations .................................................................. 13
Revision History ............................................................................... 2
Power Supplies ............................................................................ 14
Specifications..................................................................................... 3
Output Loading .......................................................................... 14
Test Circuits ....................................................................................... 6
Layout Information .................................................................... 14
Absolute Maximum Ratings ............................................................ 7
Evaluation Board ............................................................................ 15
ESD Caution .................................................................................. 7
Bill Of Materials List for AD10465 Evaluation Board ........... 19
Pin Configuration and Pin Function Descriptions ...................... 8
Silkscreens ................................................................................... 20
Typical Performance Characteristics ............................................. 9
Outline Dimensions ....................................................................... 24
Terminology .................................................................................... 11
Ordering Guide .......................................................................... 24
REVISION HISTORY
7/15—Rev. A to Rev. B
Updated Outline Dimensions ....................................................... 24
Changes to Ordering Guide .......................................................... 24
3/06—Rev. 0 to Rev. A
Remove AZ Grade .............................................................. Universal
Changes to General Description Section ...................................... 1
Changes to Table 1 ............................................................................ 3
Inserted Test Circuits Section ......................................................... 6
Updates to Ordering Guide ........................................................... 24
1/01—Revision 0: Initial Version
Rev. B | Page 2 of 24
Data Sheet
AD10465
SPECIFICATIONS
AVCC = +5 V; AVEE = –5 V; DVCC = 3.3 V applies to each ADC, unless otherwise noted. All specifications guaranteed within 100 ms of
initial power-up, regardless of sequencing.
Table 1.
Parameter
RESOLUTION
DC ACCURACY
No Missing Codes
Offset Error
Offset Error Channel Match
Gain Error2
Gain Error Channel Match
ANALOG INPUT (AIN)
Input Voltage Range
AIN1
AIN2
AIN3
Input Resistance
AIN1
AIN2
AIN3
Input Capacitance3
Analog Input Bandwidth4
ENCODE INPUT (ENC, ENC)5
Differential Input Voltage
Differential Input Resistance
Differential Input Capacitance
SWITCHING PERFORMANCE
Maximum Conversion Rate6
Minimum Conversion Rate6
Aperture Delay (tA)
Aperture Delay Matching
Aperture Uncertainty (Jitter)
ENCODE Pulse Width High
ENCODE Pulse Width Low
Output Delay (tOD)
ENCODE, Rising to Data Ready, Rising Delay (TE_DR)
SNR7
Analog Input @ 4.98 MHz
Analog Input @ 9.9 MHz
Analog Input @ 19.5 MHz
Analog Input @ 32.1 MHz
Temp
Test1
Level
Mil
Subgroup
Full
25°C
Full
Full
25°C
Full
25°C
Max
Min
VI
I
VI
V
I
VI
I
I
I
1, 2, 3
1
2, 3
Full
Full
Full
V
V
V
Full
Full
Full
25°C
Full
IV
IV
IV
IV
V
Full
25°C
25°C
IV
V
V
Full
Full
25°C
25°C
25°C
25°C
25°C
Full
Full
VI
V
V
IV
V
IV
IV
V
25°C
25°C
Full
25°C
Full
25°C
Full
V
I
II
I
II
I
II
1
2, 3
1
2
3
Min
−2.2
−2.2
−1
−3
−5
−1.5
−3
−5
AD10465BZ/QML-H
Typ
Max
14
Guaranteed
±0.02
±1.0
±1.0
−1.0
±2.0
±0.5
±1.0
+2.2
+2.2
+1
+1
+5
+1.5
+3
+5
±0.5
±1.0
±2
12
12
12
12
99
198
396
0
100
200
400
4.0
100
101
202
404
7.0
65
20
12
12
6.2
6.2
4
5, 6
4
5, 6
4
5, 6
69
68
68
67
67
67
Rev. B | Page 3 of 24
1.5
250
0.3
7.7
7.7
6.8
11.5
70
70
70
70
70
69
69
Ω
Ω
Ω
pF
MHz
V p-p
kΩ
pF
10
2.5
12
% FS
% FS
%
% FS
% FS
%
%
%
V
V
V
0.4
4, 5, 6
12
Unit
Bits
500
9.2
9.2
MSPS
MSPS
ns
ps
ps rms
ns
ns
ns
ns
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
AD10465
Parameter
SINAD8
Analog Input @ 4.98 MHz
Analog Input @ 9.9 MHz
Analog Input @ 19.5 MHz
Analog Input @ 32.1 MHz
SPURIOUS-FREE DYNAMIC RANGE9
Analog Input @ 4.98 MHz
Analog Input @ 9.9 MHz
Analog Input @ 19.5 MHz
Analog Input @ 32.1 MHz
TWO-TONE IMD REJECTION10
fIN = 10 MHz and 11 MHz
f1 and f2 are −7 dB
fIN = 31 MHz and 32 MHz
f1 and f2 Are −7 dB
CHANNEL-TO-CHANNEL ISOLATION11
TRANSIENT RESPONSE
OVERVOLTAGE RECOVERY TIME
VIN = 2.0 × fS
VIN = 4.0 × fS
DIGITAL OUTPUTS12
Logic Compatibility
DVCC = 3.3 V
Logic 1 Voltage
Logic 0 Voltage
DVCC = 5 V
Logic 1 Voltage
Logic 0 Voltage
Output Coding
POWER SUPPLY
AVCC Supply Voltage13
I (AVCC) Current
AVEE Supply Voltage13
I (AVEE) Current
DVCC Supply Voltage13
I (DVCC) Current
ICC (Total) Supply Current per Channel
Power Dissipation (Total)
Power Supply Rejection Ratio (PSRR)
Passband Ripple to 10 MHz
Passband Ripple to 25 MHz
Data Sheet
Temp
Test1
Level
Mil
Subgroup
Min
AD10465BZ/QML-H
Typ
Max
25°C
25°C
Full
25°C
Full
25°C
Full
V
I
II
I
II
I
II
4
5, 6
4
5, 6
4
5, 6
67.5
67.5
65
65
60
58
70
69
69
68
68
63
61
dB
dB
dB
dB
dB
dB
dB
25°C
25°C
Full
25°C
Full
25°C
Full
V
I
II
I
II
I
II
4
5, 6
4
5, 6
4
5, 6
73
70
72
70
62
60
85
82
82
78
78
68
66
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
25°C
4
5, 6
4
5, 6
12
78
78
68
60
87
25°C
Full
25°C
25°C
I
II
I
II
IV
V
dBFS
dBFS
dBFS
dBFS
dB
ns
Full
Full
IV
IV
12
12
70
90
15.3
40
150
Unit
100
200
ns
ns
0.5
V
V
CMOS
Full
Full
I
I
Full
Full
V
V
Full
Full
Full
Full
Full
Full
Full
Full
Full
VI
I
VI
V
VI
V
I
I
V
V
V
1, 2, 3
1, 2, 3
2.5
DVCC − 0.2
0.2
DVCC − 0.3
0.35
Twos complement
4.85
−5.25
3.135
1, 2, 3
1, 2, 3
Rev. B | Page 4 of 24
5.0
270
−5.0
38
3.3
30
338
3.5
0.02
0.1
0.2
5.25
308
−4.75
49
3.465
46
403
3.9
V
V
V
mA
V
mA
V
mA
mA
W
% FSR/% VS
dB
dB
Data Sheet
AD10465
See Table 3.
Gain tests are performed on AIN1 input voltage range.
3
Input capacitance specification combines AD8037 die capacitance and ceramic package capacitance.
4
Full power bandwidth is the frequency at which the spectral power of the fundamental frequency (as determined by FFT analysis) is reduced by 3 dB.
5
All ac specifications tested by driving ENCODE and ENCODE differentially.
6
Minimum and maximum conversion rates allow for variation in encode duty cycle of 50% ± 5%.
7
Analog input signal power at –1 dBFS; signal-to-noise ratio (SNR) is the ratio of signal level to total noise (first five harmonics removed). ENCODE = 65 MSPS. SNR is
reported in dBFS, related back to converter full power.
8
Analog input signal power at –1 dBFS. Signal-to-noise and distortion (SINAD) is the ratio of signal level to total noise + harmonics. ENCODE = 65 MSPS.
9
Analog input signal power swept from −1 dBFS to −60 dBFS; SFDR is the ratio of converter full scale to worst spur.
10
Both input tones at −7 dBFS; two-tone intermodulation distortion (IMD) rejection is the ratio of either tone to the worst third order intermodulation product.
11
Channel-to-channel isolation tested with A channel grounded and a full-scale signal applied to B channel.
12
Digital output logic levels: DVCC = 3.3 V, CLOAD = 10 pF. Capacitive loads > 10 pF degrade performance.
13
Supply voltage recommended operating range. AVCC can be varied from 4.85 V to 5.25 V. However, rated ac (harmonics) performance is valid only over the range
AVCC = 5.0 V to 5.25 V.
1
2
Rev. B | Page 5 of 24
AD10465
Data Sheet
TEST CIRCUITS
tA
N+3
N
AIN
N+1
N+2
tENC
tENCH
N
ENC, ENC
N+4
tENCL
N+1
N+2
N+3
N+4
tOD
tE, DR
D[13:0]
N–2
N–1
N
02356-015
N–3
DRY
Figure 2. Timing Diagram
AVIN3
DVCC
200Ω
AVIN2
CURRENT MIRROR
100Ω
TO AD8037
AVIN1
02356-016
100Ω
DVCC
Figure 3. Analog Input Stage
VREF
DR_OUT
LOADS
AVCC
AVCC
AVCC
AVCC
10kΩ
02356-018
CURRENT MIRROR
ENCODE
ENCODE
10kΩ
LOADS
Figure 5. Digital Output Stage
02356-017
10kΩ
DVCC
Figure 4. ENCODE Inputs
CURRENT MIRROR
DVCC
VREF
100Ω
CURRENT MIRROR
Figure 6. Digital Output Stage
Rev. B | Page 6 of 24
D0 TO
D13
02356-019
10kΩ
Data Sheet
AD10465
ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter
ELECTRICAL
VCC Voltage
VEE Voltage
Analog Input Voltage
Analog Input Current
Digital Input Voltage (ENCODE)
ENCODE, ENCODE Differential Voltage
Digital Output Current
ENVIRONMENTAL1
Operating Temperature Range (Case)
Maximum Junction Temperature
Lead Temperature (Soldering, 10 sec)
Storage Temperature Range (Ambient)
1
Min
Max
Units
0
–7
VEE
−10
0
+7
0
VCC
+10
VCC
4
+10
V
V
V
mA
V
V
mA
+85
174
300
+150
°C
°C
°C
°C
−10
−40
−65
Stresses at or above those listed under Absolute Maximum
Ratings may cause permanent damage to the product. This is a
stress rating only; functional operation of the product at these
or any other conditions above those indicated in the operational
section of this specification is not implied. Operation beyond
the maximum operating conditions for extended periods may
affect product reliability.
Table 3. Test Levels
Level
I
II
III
IV
Typical thermal impedance for 68-lead CLCC package: θJC = 2.2°C/W; θJA =
24.3°C/W.
V
VI
Description
100% production tested.
100% production tested at 25°C, and sample tested at
specified temperatures. AC testing done on sample
basis.
Sample tested only.
Parameter is guaranteed by design and characterization
testing.
Parameter is a typical value only.
100% production tested at 25°C, sample tested at
temperature extremes.
ESD CAUTION
Rev. B | Page 7 of 24
AD10465
Data Sheet
2
AGNDA 10
AGNDB
AINB2
1 68 67 66 65 64 63 62 61
3
AINB1
4
AGNDB
AINB3
5
AVCC
SHIELD
AGNDB
6
AVEE
AGNDA
REF_A
AGNDA
7
8
AINA1
AINA2
9
AGNDA
AGNDA
AINA3
PIN CONFIGURATION AND PIN FUNCTION DESCRIPTIONS
60 AGNDB
PIN 1
IDENTIFIER
AGNDA 11
59 AGNDB
DRAOUT 12
AVEE 13
58 AGNDB
57 AGNDB
AVCC 14
56 REF_B
D0A (LSBA) 15
55 DRBOUT
D1A 16
D2A 17
AD10465
D3A 18
TOP VIEW
(Not to Scale)
D4A 19
54 AGNDB
53 AGNDB
52 ENCODEB
51 ENCODEB
D5A 20
50 DVCC
D6A 21
49 D13B (MSBB)
D7A 22
48 D12B
D8A 23
47 D11B
D9A 24
46 D10B
D10A 25
45 D9B
DGNDA 26
44 DGNDB
02356-002
DGNDB
D8B
D7B
D6B
D5B
D3B
D4B
D2B
D1B
D0B (LSBB)
D12A
D13A (MSBA)
DVCC
D11A
DGNDA
ENCODEA
ENCODEA
27 28 29 30 31 32 33 34 35 36 37 38 39 40 41 42 43
Figure 7. Pin Configuration
Table 4. Pin Function Descriptions
Pin No.
1
2, 4, 5, 9 to11
Mnemonic
SHIELD
AGNDA
3
6
7
8
12
13
14
26, 27
15 to 25, 31 to 33
28
29
30
43, 44
34 to 42, 45 to 49
53, 54, 57 to 61, 65, 68
REF_A
AINA1
AINA2
AINA3
DRAOUT
AVEE
AVCC
DGNDA
D0A to D13A
ENCODEA
ENCODEA
DVCC
DGNDB
D0B to D13B
AGNDB
50
51
52
55
56
62
63
64
66
67
DVCC
ENCODEB
ENCODEB
DRBOUT
REF_B
AINB1
AINB2
AINB3
AVCC
AVEE
Description
Internal Ground Shield Between Channels.
A Channel Analog Ground. A ground and B ground should be connected as close to the device
as possible.
A Channel Internal Voltage Reference.
Analog Input for A Side ADC (Nominally ±0.5 V).
Analog Input for A Side ADC (Nominally ±1.0 V).
Analog Input for A Side ADC (Nominally ±2.0 V).
Data Ready A Output.
Analog Negative Supply Voltage (Nominally −5.0 V or −5.2 V).
Analog Positive Supply Voltage (Nominally 5.0 V).
A Channel Digital Ground.
Digital Outputs for ADC A. D0A (LSBA).
Complement of ENCODE.
Data Conversion Initiated on Rising Edge of ENCODE Input.
Digital Positive Supply Voltage (Nominally 5.0 V or 3.3 V).
B Channel Digital Ground.
Digital Outputs for ADC B. D0B (LSBB).
B Channel Analog Ground. A ground and B ground should be connected as close to the device
as possible.
Digital Positive Supply Voltage (Nominally 5.0 V or 3.3 V).
Data conversion initiated on rising edge of ENCODE input.
Complement of ENCODEB.
Data Ready B Output.
B Channel Internal Voltage Reference.
Analog Input for B Side ADC (Nominally ±0.5 V).
Analog Input for B Side ADC (Nominally ±1.0 V).
Analog Input for B Side ADC (Nominally ±2.0 V).
Analog Positive Supply Voltage (Nominally 5.0 V).
Analog Negative Supply Voltage (Nominally −5.0 V or −5.2 V).
Rev. B | Page 8 of 24
Data Sheet
AD10465
TYPICAL PERFORMANCE CHARACTERISTICS
0
0
ENCODE = 65MSPS
AIN = 5MHz (–1dBFS)
SNR = 71.02
SFDR = 92.11dBc
–10
–20
–30
–30
–40
–40
–50
–50
–60
–60
(dB)
–70
–70
–80
–80
3
2
–90
4
5
–100
–110
–110
02356-003
–100
–120
–130
5
6
–130
0
2.5 5.0 7.5 10.0 12.5 15.0 17.5 20.0 22.5 25.0 27.5 30.0 32.5
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 8. Single Tone @ 5 MHz
Figure 11. Single Tone @ 10 MHz
0
–20
–30
–40
–40
–50
–50
–60
–60
3
2
6
5
–90
5
6
–130
–120
–130
0
2.5 5.0 7.5 10.0 12.5 15.0 17.5 20.0 22.5 25.0 27.5 30.0 32.5
2.5 5.0 7.5 10.0 12.5 15.0 17.5 20.0 22.5 25.0 27.5 30.0 32.5
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 12. Single Tone @ 25 MHz
Figure 9. Single Tone @ 20 MHz
100
0
ENCODE = 65MSPS
–10 A = 32MHz (–1dBFS)
IN
–20 SNR = 70.22
SFDR = 66.40dBc
–30
90
SFDR
80
70
60
2
(–dBc)
–40
–50
3
–70
SINAD
50
40
–80
30
5
6
–100
20
4
–110
–120
–130
0
02356-008
–90
02356-005
(dB)
4
–110
02356-004
–110
–60
2
–100
–120
0
3
–80
4
–100
–70
02356-007
–80
–90
ENCODE = 65MSPS
AIN = 25MHz (–1dBFS)
SNR = 70.36
SFDR = 74.58dBc
–10
(dB)
(dB)
0
ENCODE = 65MSPS
–10 A = 20MHz (–1dBFS)
IN
–20 SNR = 70.71
SFDR = 79.73dBc
–30
–70
3
4
–120
2.5 5.0 7.5 10.0 12.5 15.0 17.5 20.0 22.5 25.0 27.5 30.0 32.5
0
2
–90
6
02356-006
(dB)
–20
ENCODE = 65MSPS
AIN = 10MHz (–1dBFS)
SNR = 70.79
SFDR = 86.06dBc
–10
10
0
4.9898
2.5 5.0 7.5 10.0 12.5 15.0 17.5 20.0 22.5 25.0 27.5 30.0 32.5
9.989
19.000
INPUT FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 13. SFDR and SINAD vs. Frequency
Figure 10. Single Tone @ 32 MHz
Rev. B | Page 9 of 24
32.000
AD10465
Data Sheet
0
0
ENCODE = 65MSPS
AIN = 9MHz AND
10MHz (–7dBFS)
SFDR = 82.83dBc
–10
–20
–20
–30
–30
–40
–40
–50
–50
–60
–60
(dB)
–70
–80
F2–
–90 F1
2F1+
F2
F1+
F2
2F2–
F1
2F1–
F2
2F2+
F1
2F1+
F2
2F1–
F2
F2–
F1
–80
2F2–
F1
F1+
F2
–90
–100
–110
–110
02356-009
–100
–120
–130
0
2F2+
F1
–70
02356-012
(dB)
ENCODE = 65MSPS
AIN = 17MHz AND
18MHz (–7dBFS)
SFDR = 77.68dBc
–10
–120
–130
2.5 5.0 7.5 10.0 12.5 15.0 17.5 20.0 22.5 25.0 27.5 30.0 32.5
0
2.5 5.0 7.5 10.0 12.5 15.0 17.5 20.0 22.5 25.0 27.5 30.0 32.5
FREQUENCY (MHz)
FREQUENCY (MHz)
Figure 14. Two Tone @ 9 MHz and 10 MHz
Figure 17. Two Tone @ 17 MHz and 18 MHz
3.0
3
ENCODE = 65MSPS
DNL MAX = +0.549 LSB
DNL MIN = –0.549 LSB
2.5
ENCODE = 65MSPS
INL MAX = +1.173 LSB
INL MIN = –1.332 LSB
2
2.0
1
(LSB)
(LSB)
1.5
1.0
0
0.5
–1
0
02356-010
–1.0
0
2048
4096
6144
8192
10240
12288
14336
02356-013
–2
–0.5
–3
0
16384
2048
4096
6144
CODES
10240
12288
14336
16384
Figure 18. Integral Nonlinearity
Figure 15. Differential Nonlinearity
0
72.0
–1
71.5
–2
71.0
SNR FULL SCALE
–3
–4
–5
–6
–40°C
70.5
+25°C
70.0
+85°C
69.5
69.0
–7
–9
–10
1.0
4.2
7.4
10.6
13.8
17.0
20.2
23.4
26.6
29.8
02356-014
68.5
–8
68.0
02356-011
(dBFS)
8192
CODES
67.5
5
33.0
10
19
AIN (MHz)
FREQUENCY (MHz)
Figure 16. Gain Flatness
Figure 19. SNR vs. AIN Frequency
Rev. B | Page 10 of 24
32
Data Sheet
AD10465
TERMINOLOGY
Analog Bandwidth
The analog input frequency at which the spectral power of the
fundamental frequency (as determined by the FFT analysis) is
reduced by 3 dB.
Aperture Delay
The delay between a differential crossing of ENCODE and
ENCODE, and the instant at which the analog input is sampled.
Aperture Uncertainty (Jitter)
The sample-to-sample variation in aperture delay.
Output Propagation Delay
The delay between a differential crossing of ENCODE and
ENCODE, and the time when all output data bits are within
valid logic levels.
Overvoltage Recovery Time
The amount of time required for the converter to recover to
0.02% accuracy after an analog input signal of the specified
percentage of full scale is reduced to midscale.
Differential Nonlinearity
The deviation of any code from an ideal 1 LSB step.
Power Supply Rejection Ratio
The ratio of a change in input offset voltage to a change in
power supply voltage.
ENCODE Pulse Width/Duty Cycle
Pulse width high is the minimum amount of time that the
ENCODE pulse should be left in Logic 1 state to achieve rated
performance; pulse width low is the minimum time ENCODE
pulse should be left in low state. At a given clock rate, these
specs define an acceptable encode duty cycle.
Signal-to-Noise and Distortion (SINAD)
The ratio of the rms signal amplitude (set at 1 dB below full
scale) to the rms value of the sum of all other spectral components, including harmonics but excluding dc. Can be reported
in dB (that is, relative to signal level) or in dBFS (always related
back to converter full scale).
Harmonic Distortion
The ratio of the rms signal amplitude to the rms value of the
worst harmonic component.
Signal-to-Noise Ratio (Without Harmonics)
The ratio of the rms signal amplitude (set at 1 dB below full
scale) to the rms value of the sum of all other spectral components, excluding the first five harmonics and dc. Can be
reported in dB (that is, relative to signal level) or in dBFS
(always related back to converter full scale).
Integral Nonlinearity
The deviation of the transfer function from a reference line
measured in fractions of 1 LSB using a “best straight line”
determined by a least square curve fit.
Minimum Conversion Rate
The encode rate at which the SNR of the lowest analog signal
frequency drops by no more than 3 dB below the guaranteed
limit.
Maximum Conversion Rate
The encode rate at which parametric testing is performed,
above which converter performance can degrade.
Spurious-Free Dynamic Range
The ratio of the rms signal amplitude to the rms value of the
peak spurious spectral component. The peak spurious
component may or may not be a harmonic.
Transient Response
The time required for the converter to achieve 0.03% accuracy
when a one-half, full-scale step function is applied to the analog
input.
Two-Tone Intermodulation Distortion Rejection
The ratio of the rms value of either input tone to the rms value
of the worst third-order intermodulation product; reported in
dBFS.
Rev. B | Page 11 of 24
AD10465
Data Sheet
THEORY OF OPERATION
The AD10465 is a high dynamic range, 14-bit, 65 MHz pipeline
delay (three pipelines) analog-to-digital converter. The custom
analog input section maintains the same input ranges (1 V p-p,
2 V p-p, and 4 V p-p) and input impedance (100 Ω, 200 Ω, and
400 Ω) as the AD10242.
The AD10465 employs four monolithic Analog Devices
components per channel (AD8037, AD8138, AD8031, and
AD6644), along with multiple passive resistor networks and
decoupling capacitors to fully integrate a complete 14-bit
analog-to-digital converter.
The input signal is passed through a precision laser trimmed
resistor divider allowing the user to externally select operation
with a full-scale signal of ±0.5 V, ±1.0 V, or ±2.0 V by choosing
the proper input terminal for the application.
The AD10465 analog input includes an AD8037 amplifier
featuring an innovative architecture that maximizes the
dynamic range capability on the amplifiers inputs and outputs.
The AD8037 amplifier provides a high input impedance and
gain for driving the AD8138 in a single-ended to differential
amplifier configuration. The AD8138 has a −3 dB bandwidth at
300 MHz and delivers a differential signal with the lowest
harmonic distortion available in a differential amplifier. The
AD8138 differential outputs help balance the differential inputs
to the AD6644, maximizing the performance of the ADC.
The AD8031 provides the buffer for the internal reference of the
AD6644. The internal reference voltage of the AD6644 is
designed to track the offsets and drifts of the ADC and is used
to ensure matching over an extended temperature range of
operation. The reference voltage is connected to the output
common-mode input on the AD8138. The AD6644 reference
voltage sets the output common mode on the AD8138 at 2.4 V,
which is the midsupply level for the AD6644.
The AD6644 has complementary analog input pins, AIN and
AIN. Each analog input is centered at 2.4 V and should swing
±0.55 V around this reference. Since AIN and AIN are 180° out
of phase, the differential analog input signal is 2.2 V peak-topeak. Both analog inputs are buffered prior to the first trackand-hold, TH1. The high state of the ENCODE pulse places
TH1 in hold mode. The held value of TH1 is applied to the
input of a 5-bit coarse ADC1. The digital output of ADC1
drives 14 bits of precision, which is achieved through laser
trimming. The output of DAC1 is subtracted from the delayed
analog signal at the input of TH3 to generate a first residue
signal. TH2 provides an analog pipeline delay to compensate for
the digital delay of ADC1.
The first residue signal is applied to a second conversion stage
consisting of a 5-bit ADC2, 5-bit DAC2, and pipeline TH4. The
second DAC requires 10 bits of precision, which is met by the
process with no trim. The input to TH5 is a second residue
signal generated by subtracting the quantized output of DAC2
from the first residue signal held by TH4. TH5 drives a final
6-bit ADC3.
The digital outputs from ADC1, ADC2, and ADC3 are added
together and corrected in the digital error correction logic to
generate the final output data. The result is a 14-bit parallel
digital CMOS-compatible word, coded as twos complement.
USING THE FLEXIBLE INPUT
The AD10465 has been designed with the user’s ease of operation in mind. Multiple input configurations have been included
on board to allow the user a choice of input signal levels and
input impedance. While the standard inputs are ±0.5 V, ±1.0 V,
and ±2.0 V, the user can select the input impedance of the
AD10465 on any input by using the other inputs as alternate
locations for GND or an external resistor. Table 5 summarizes
the impedance options available at each input location.
Table 5. Input Impedance Options
Input
AIN1
AIN2
AIN3
Impedance
100 Ω
75 Ω
50 Ω
200 Ω
100 Ω
75 Ω
50 Ω
400 Ω
100 Ω
75 Ω
50 Ω
Condition
When AIN2 and AIN3 are open
When AIN3 is shorted to GND
When AIN2 is shorted to GND
When AIN3 is open
When AIN3 is shorted to GND
When AIN2 to AIN3 has an external resistor of 300 Ω, with AIN3 shorted to GND
When AIN2 to AIN3 has an external resistor of 100 Ω, with AIN3 shorted to GND
When AIN3 has an external resistor of 133 Ω to GND
When AIN3 has an external resistor of 92 Ω to GND
When AIN3 has an external resistor of 57 Ω to GND
Rev. B | Page 12 of 24
Data Sheet
AD10465
APPLYING THE AD10465
ENCODING THE AD10465
JITTER CONSIDERATIONS
The AD10465 encode signal must be a high quality, extremely
low phase noise source to prevent degradation of performance.
Maintaining 14-bit accuracy places a premium on encode clock
phase noise. SNR performance can easily degrade by 3 dB to
4 dB with 32 MHz input signals when using a high jitter clock
source. See the Analog Devices Application Note AN-501, Aperture Uncertainty and ADC System Performance, for complete
details. For optimum performance, the AD10465 must be
clocked differentially. The encode signal is usually ac-coupled
into the ENCODE and ENCODE pins via a transformer or
capacitors. These pins are biased internally and require no
additional bias.
The signal-to-noise ratio (SNR) for an ADC can be predicted.
When normalized to ADC codes, Equation 1 accurately
predicts the SNR based on three terms. These are jitter, average
DNL error, and thermal noise. Each of these terms contributes
to the noise within the converter.
Figure 20 shows one preferred method for clocking the
AD10465. The clock source (low jitter) is converted from
single-ended to differential using an RF transformer. The backto-back Schottky diodes across the transformer secondary limit
clock excursions into the AD10465 to approximately 0.8 V p-p
differential. This helps prevent the large voltage swings of the
clock from feeding through to the other portions of the
AD10465, and limits the noise presented to the ENCODE
inputs. A crystal clock oscillator can also be used to drive the
RF transformer if an appropriate limiting resistor (typically
100 Ω) is placed in the series with the primary.
T1-4T
ENCODE
AD10465
02356-020
ENCODE
HSMS2812
DIODES
Figure 20. Crystal Clock Oscillator, Differential ENCODE
If a low jitter ECL/PECL clock is available, another option is to
ac couple a differential ECL/PECL signal to the ENCODE and
ENCODE input pins as shown in Figure 21. A device that offers
excellent jitter performance is the MC100LVEL16 (or same
family) from Motorola.
(1)
tj rms is the rms jitter of the encode (rms sum of encode source
and internal encode circuitry).
ε is the average DNL of the ADC (typically 0.50 LSB).
N is the number of bits in the ADC.
VNOISE rms is the V rms noise referred to the analog input of the
ADC (typically 5 LSB).
For a 14-bit analog-to-digital converter like the AD10465,
aperture jitter can greatly affect the SNR performance as the
analog frequency is increased. The chart below shows a family
of curves that demonstrates the expected SNR performance of
the AD10465 as jitter increases. The chart is derived from
Equation 1.
For a complete discussion of aperture jitter, please consult the
Analog Devices Application Note AN-501, Aperture Uncertainty
and ADC System Performance.
71
VT
AIN = 5MHz
70
0.1µF
69
ENCODE
68
AD10465
AIN = 10MHz
67
66
65
AIN = 20MHz
64
63
62
RMS CLOCK JITTER (ps)
Figure 22. SNR vs. Jitter
Rev. B | Page 13 of 24
02356-022
3.9
3.7
2.9
2.7
2.5
2.3
2.1
1.9
1.7
1.5
1.3
1.1
0.9
0.7
60
3.5
AIN = 32MHz
61
0.1
Figure 21. Differential ECL for ENCODE
SNR (dBFS)
VT
02356-021
ENCODE
0.5
0.1µF
0.3
ECL/
PECL
1/ 2
fANALOG is the analog input frequency.
3.3
0.1nF 100Ω









where:
3.1
CLOCK
SOURCE
 1 
 N  
 2 

2
SNR   20  log 2    f ANALOG  t j rms 

2
 v NOISE rms 
 2 n 


AD10465
Data Sheet
POWER SUPPLIES
LAYOUT INFORMATION
Care should be taken when selecting a power source. Linear
supplies are strongly recommended. Switching supplies tend to
have radiated components that can be “received” by the
AD10465. Each of the power supply pins should be decoupled
as closely to the package as possible using 0.1 μF chip
capacitors.
The schematic of the evaluation board (see Figure 24)
represents a typical implementation of the AD10465. The
pinout of the AD10465 is very straightforward and facilitates
ease of use and the implementation of high frequency/high
resolution design practices. It is recommended that high quality
ceramic chip capacitors be used to decouple each supply pin to
ground directly at the device. All capacitors can be standard
high quality ceramic chip capacitors.
The AD10465 has separate digital and analog power supply
pins. The analog supplies are denoted AVCC and the digital
supply pins are denoted DVCC. AVCC and DVCC should be
separate power supplies. This is because the fast digital output
swings can couple switching current back into the analog supplies. Note that AVCC must be held within 5% of 5 V. The
AD10465 is specified for DVCC = 3.3 V as this is a common
supply for digital ASICs.
OUTPUT LOADING
Care should be taken when placing the digital output runs.
Because the digital outputs have such a high slew rate, the
capacitive loading on the digital outputs should be minimized.
Circuit traces for the digital outputs should be kept short and
connect directly to the receiving gate. Internal circuitry buffers
the outputs of the ADC through a resistor network to eliminate
the need to externally isolate the device from the receiving gate.
Care must be taken when designing the data receivers for the
AD10465. The digital outputs drive an internal series resistor (for
example, 100 Ω) followed by a gate, such as the 75LCX574. To
minimize capacitive loading, there should only be one gate on each
output pin. An example of this is shown in the evaluation board
schematic shown in Figure 26. The digital outputs of the AD10465
have a constant output slew rate of 1 V/ns. A typical CMOS gate
combined with a PCB trace has a load of approximately 10 pF.
Therefore, as each bit switches, 10 mA (10 pF × 1 V ÷1 ns) of
dynamic current per bit flows in or out of the device. A full-scale
transition can cause up to 140 mA (14 bits ×10 mA/bit) of current
flow through the output stages. These switching currents are
confined between ground and the DVCC pin. Standard TTL gates
should be avoided because they can appreciably add to the dynamic
switching currents of the AD10465. It should also be noted that
extra capacitive loading increases output timing and invalidates
timing specifications. Digital output timing is guaranteed with
10 pF loads.
Rev. B | Page 14 of 24
Data Sheet
AD10465
EVALUATION BOARD
Power to the analog supply pins is connected via banana jacks.
The analog supply powers the associated components and the
analog section of the AD10465. The digital outputs of the
AD10465 are powered via banana jacks with 3.3 V. Contact the
factory if additional layout or applications assistance is required.
02356-023
The AD10465 evaluation board (Figure 23) is designed to
provide optimal performance for evaluation of the AD10465
analog-to-digital converter. The board encompasses everything
needed to ensure the highest level of performance for evaluating
the AD10465. The board requires an analog input signal,
encode clock, and power supply inputs. The clock is buffered
on-board to provide clocks for the latches. The digital outputs
and clocks are available at the standard 40-pin connectors,
Connector J1 and Connector J2.
Figure 23. Evaluation Board Mechanical Layout
Rev. B | Page 15 of 24
AD10465
Data Sheet
JP5
J1
CLKLATCHB2
AINB3
LATCHB
11
4
U2:B
74LCX00M
JP1
BUFLATB
JP2
BUFLATA
6
5
12
74LCX00M
AINB2
U2:D
13
3
2
JP3
J2
U2:A
1
CLKLATCHB1
AGNDB
74LCX00M
DRBOUT
DRAOUT
AGNDB
J22
1
JP4
U4:A
2
AINB1
U4:D
13
3
11
12
4
U4:B
6
5
CLKLATCHA1
74LCX00M
AGNDB
74LCX00M
74LCX00M
JP6
CLKLATCHA2
J7
LATCHA
AINA3
AGNDA
47V
AT 100MHz
L9
–5.2VAB
J8
AINA2
47V
AT 100MHz
L8
47
C59
10µF
+5VAB
47
C52
10µF
AGNDA
AINB1
AINB3
+5VAB
AINB2
AGNDB
AGNDA
C57
0.1µF
AINA1
AINA3
AINA1
AINA2
AGNDB
J20
AGNDB
62
61
AINB1
AINB2
AINB3
66
65
64
63
+5VAB
AGNDB
–5.2VAB
AGNDB
SHIELD
REFA
AGNDA
AGNDA
AGNDA
D5A
+3.3VDB
D6A
D13B (MSB)
D7A
D12B
D8A
D11B
D9A
D10B
L11
+3.3VDA
C62
10µF
DGNDA
47
D9B
DGNDB
C61
0.1µF
DRBOUT
AGNDB
52
51
50
49
48
47
46
45
44
ENCBB
ENCB
DUT_3.3VDB
D13B (MSB) C64
0.1µF
D12B
D11B
D10B
D9B
L6
47
+3.3VDB
C58
10µF
DGNDB
AGNDB
D8B
D7B
D6B
D11A
DUT_+3.3VDA
DGNDA
D5B
DGNDA
D4B
D10A
60
59
58
57
56
55
54
53
DGNDB
DUT_3.3VDB
DUT_3.3VDA
C63
0.1µF
DGNDA
10
C26
0.1µF
SPARE
GATE
U2:C
9
8
SPARE
GATE
U4:C
10
C27
0.1µF
9
74LCX00M
DGNDB
DGNDB
Figure 24. Evaluation Board
Rev. B | Page 16 of 24
8
74LCX00M
DGNDA
DGNDA
02356-024
AINA1
7
6
5
4
3
2
AINA2
1
68
67
ENCB
D3B
D10A
ENCBB
AD10465
D4A
D2B
D9A
D3A
D1B
D8A
U1
D0B
D7A
AGNDB
D2A
D12A
33
D13A (MSB)
34
D0B (LSB)
35
D1B
36
D2B
37
D3B
38
D4B
39
D5B
40
D6B
41
D7B
42
D8B
43
DGNDB
D6A
AGNDB
D1A
D13A
D5A
DRBOUT
D0A (LSB)
D12A
D4A
REFB
+5VAA
D11A
D3A
AGNDB
ENCA
AGNDA
D2A
AGNDB
–5.2VAA
27
28
29
30
31
C53
10µF
47
47Ω
AT 100MHz
D1A
DRAOUT
ENCAB
L7
AGNDB
32
D0A
AGNDB
AGNDA
+3.3VDA
+5VAA
+5VAA
AGNDA
ENCA
DRAOUT
AGNDA
10
11
12
13
14
15
16
17
18
19
20
21
22
23
24
25
26
ENCAB
47
C22
10µF
DGNDA
L10
AGNDA
AGNDA
–5.2VAA
AINA3
9
8
AGNDA
Data Sheet
AD10465
+5VAA
U6
ADP3330
2
OUT
IN
NR
6
SD
+5VAA
ERR
1
C45
100pF
8
3
AGNDA
GND
C42
0.1µF
J6
4
JP11
OPEN
ENCODEA
AGNDA
R140
33kΩ
R82
51Ω
C44
0.1µF
U7
1
AGNDA
2
C40
0.1µF
J18
AGNDA
NC
D
AGNDA
JP8 JP7
ENCA
Q
VBB
5
VEE
R94
100Ω
AGNDA
AGNDA
+5VAA
R89
100Ω
C41
0.47µF
MC10EP16D
NC = NO CONNECT
AGNDA
C49
0.1µF
6
D
4
R83
51Ω
7
Q
3
ENCODEA
ENCAB
8
VCC
AGNDA
U8
ADP3330
2
OUT
IN
NR
6
SD
+5VAA
ERR
1
C43
100pF
8
3
AGNDB
GND
ENCODEB
AGNDB
R141
33kΩ
R76
51Ω
1
2
C39
0.1µF
C48
0.1µF
NC
D
AGNDB
Q
4
JP10 JP9
8
7
C46
0.1µF
6
D
R79
51Ω
ENCB
VCC
3
ENCODEB
AGNDB
AGNDB
U9
AGNDB
J17
4
JP12
OPEN
VBB
ENCBB
Q
VEE
5
C38
0.47µF
R95
100Ω
MC10EP16D
NC = NO CONNECT AGNDB
AGNDB
Figure 25. Evaluation Board
Rev. B | Page 17 of 24
AGNDB
R97
100Ω
02356-025
C37
0.1µF
J16
AD10465
Data Sheet
OUT_3.3VDA
R117
100Ω
OUT_3.3VDA
U21
C14
0.1µF
C15
0.1µF
C20
0.1µF
VCC
LATCHA
R98
51Ω
24
DGNDA
BANANA JACKS FOR GNDS AND PWRS
(LSB) D0A
+5VAB
+5VAA
R100
0Ω
+3.3VDB
R99
0Ω
+3.3VDA
E1
D1A
D2A
D3A
D4A
D5A
DGNDA
E2
D6A
E3
D7A
D8A
E4
D9A
E5
D10A
D11A
E6
D12A
(MSB) D13A
E7
25
E8
E9
E10
VCC
CP2
VCC
OE2
26
I15
27
I14
29
I13
30
I12
32
I11
33
I10
35
I9
36
I8
48
CP1
1
OE1
37
I7
38
I6
40
I5
41
I4
43
I3
44
I2
46
I1
47
I0
28
GND
34
GND
39
GND
45
GND
42
31
VCC
23
O15
22
O14
20
O13
19
O12
17
O11
16
O10
14
O9
13
O8
O6
O5
O4
O3
O2
O1
O0
GND
GND
R116
100Ω
7
18
O7
R115
100Ω
12
11
9
8
6
R114
100Ω
AGNDA
–5.2VAA
AGNDB
C24
0.1µF
VCC
R119
51Ω
DGNDA
E72
E140
E141
E142
E144
E145
E147
E150
E151
E154
E185
E194
E196
E198
E200
E202
E204
E206
E223
E225
AGNDA
E162
E163
E164
E165
E166
E171
E172
E177
1E79
E181
E186
E187
E207
E209
E211
E213
E215
E217
E219
E221
E227
E229
E231
E233
AGNDB
(LSB) D0B
R123
0Ω
25
24
DGNDB
E159
E160
E161
E167
E168
E169
E170
E178
E180
E182
E183
E191
E192
E193
E208
E210
E212
E214
E216
E218
E220
E222
E228
E230
E232
E234
R124 D1B
0Ω
D2B
D3B
D4B
D5B
DGNDB
D6B
D7B
D8B
D9B
D10B
D11B
D12B
(MSB) D13B
9
8
21
19
22
18
23
17
24
16
25
15
26
14
27
13
28
12
29
11
30
10
31
9
32
8
33
R108
100Ω
R107
100Ω
21
22
23
24
25
26
27
28
29
30
31
32
33
34
34
35
35
36
36
37
37
38
38
39
39
40
40
7
7
6
6
5
5
4
4
3
3
2
2
1
1
R109
100Ω
J3
R110
100Ω
DGNDA
MSB
R112
100Ω
VCC
CP2
OE2
26
I15
27
I14
29
I13
30
I12
32
I11
33
I10
35
I9
36
I8
48
CP1
1
OE1
37
I7
38
I6
40
I5
41
I4
43
I3
44
I2
46
I1
47
I0
28
GND
34
GND
39
GND
45
GND
VCC
42
31
VCC
23
O15
22
O14
20
O13
19
O12
17
O11
16
O10
14
O9
13
O8
O6
O5
O4
O3
O2
O1
O0
GND
GND
R126
100Ω
7
18
O7
R127
100Ω
12
11
9
8
6
R125
100Ω
R134
100Ω
R137
51Ω
BUFLATB
R135
100Ω
R136
100Ω
R131
100Ω
R132
100Ω
15
18
GND
4
GND
R133
100Ω
R120
100Ω
DGNDB
Rev. B | Page 18 of 24
20
21
19
22
18
23
17
17
16
16
15
15
14
14
13
13
12
12
11
11
10
10
9
9
8
8
7
7
6
6
5
5
4
4
3
3
2
2
1
1
24
25
26
27
28
29
30
31
32
33
34
35
36
37
38
39
40
21
22
23
24
25
26
27
28
29
30
31
32
33
34
35
36
37
38
39
40
J4
R121
100Ω
R122
100Ω
Figure 26. Evaluation Board
18
R128
100Ω
3
21
19
R129
100Ω
5
2
20
R130
100Ω
74LCX163743MTD
DGNDB
11
20
DGNDA
DGNDA
LATCHB
E87
E88
E89
E139
E143
E146
E148
E149
E152
E153
E184
E188
E189
E190
E195
E197
E199
E201
E203
E205
E224
E226
12
10
R101
100Ω
OUT_3.3VDB
C23
0.1µF
13
R102
100Ω
U22
C21
0.1µF
14
R111
100Ω
OUT_3.3VDA
C25
0.1µF
15
BUFLATA
R103
100Ω
18
DGNDB
16
R118
51Ω
74LCX163743MTD
–5.2VAB
17
R106
100Ω
15
GND
4
GND
18
R104
100Ω
3
2
19
R105
100Ω
5
21
20
R113
100Ω
DGNDB
MSB
02356-026
C13
0.1µF
Data Sheet
AD10465
BILL OF MATERIALS LIST FOR AD10465 EVALUATION BOARD
Table 6. Bill of Materials
Qty
2
Reference Designator
U2, U4
2
U21, U22
1
U1
2
U6, U8
Description
IC, low-voltage Quad 2-input nand,
SOIC-14
IC, 16-bit transparent latch with
three-state outputs, TSSOP-48
DUT, IC 14-bit analog-to-digital
converter
IC, voltage regulator 3.3 V, RT-6
10
E1 to E10
Banana jack, socket
22
C13 to C15, C20, C21,
C23 to C27, C37, C39,
C40, C42, C44, C46,
C48, C49, C57, C61,
C63, C64
C38, C41
C43, C45
J3, J4
L6 to L11
2
2
2
6
2
6
4
2
8
36
8
U7, U9
C22, C52, C53, C58,
C59, C62
R99, R100, R123, R124
R140, R141
R76, R79, R82, R83, R98,
R118, R119, R137
R89, R94, R95, R97,
R101 to R117, R120 to
R122, R125 to R136
J1, J2, J6 to J8, J16 to
J18, J20, J22
Value
Manufacturer and Part
Number
Toshiba/TC74LCX00FN
Component
Name
74LCX00M
Fairchild/74LCX163743MTD
74LCX163743MTD
ADI/AD10465BZ
ADI/AD10465BZ
Analog Devices/ADP3330ART3, 3-RLT
Johnson Components/080740-001
Mena/GRM40X7R104K025BL
ADP3330
CAP 0805
Banana Hole
0.1 μF
Capacitor, 0.1 μF, 20%, 12 V dc, 0805
0.47 μF
100 pF
Vitramon/VJ1206U474MFXMB
Johansen/500R15N101JV4
Samtec/TSW-120-08-G-D
Fair-Rite/2743019447
CAP 1206
CAP 0805
HD40M
IND2
Motorola/MC10EP16D
Kemet/T491C106M016A57280
MC10EP16D
POLCAP 1812
Panasonic/ERJ-6GEY0R00V
Panasonic/ERJ-6GEYJ333V
RES2 0805
RES2 0805
51 Ω
Capacitor, 0.47 μF, 5%, 12 V dc, 1206
Capacitor, 100 pF, 10%, 12 V dc, 0805
Connector, 40-pin header male
Inductor, 47 μH @ 100 MHz, 20%,
IND2
IC, differential receiver, SOIC-8
Capacitor, 10 μF, 20%, 16 V dc,
1812POL
Resistor, 0.0 Ω, 0805
Resistor, 33,000 Ω, 5%, 0.10 Watt,
0805
Resistor, 51 Ω, 5%, 0.10 Watt, 0805
Panasonic/ERJ-6GEYJ510V
100 Ω
Resistor, 100 Ω, 5%, 0.10 Watt, 0805
Panasonic/ERJ-6GEYJ101V
RES2 0805, RES
0805
RES2 0805, RES
0805
Connector, SMA female
Johnson Components/1420701-201
47 μH
10 μF
0.0 Ω
33,000 Ω
Rev. B | Page 19 of 24
SMA
AD10465
Data Sheet
02356-027
SILKSCREENS
02356-028
Figure 27. Top Layer Copper
Figure 28. Second Layer Copper
Rev. B | Page 20 of 24
AD10465
02356-029
Data Sheet
02356-030
Figure 29. Third Layer Copper
Figure 30. Fourth Layer Copper
Rev. B | Page 21 of 24
Data Sheet
02356-031
AD10465
02356-032
Figure 31. Fifth Layer Copper
Figure 32. Bottom Layer Copper
Rev. B | Page 22 of 24
AD10465
02356-033
Data Sheet
02356-034
Figure 33. Bottom Silkscreen
Figure 34. Bottom Assembly
Rev. B | Page 23 of 24
AD10465
Data Sheet
OUTLINE DIMENSIONS
0.010 (0.25)
0.008 (0.20)
0.007 (0.18)
0.235 (5.97)
MAX
0.960 (24.38)
0.950 (24.13) SQ
0.940 (23.88)
9
61
10
60
PIN 1
TOE DOWN
ANGLE
0–8 DEGREES
1.070
(27.18)
MIN
TOP VIEW
0.800
(20.32)
BSC
1.190 (30.23)
1.180 (29.97) SQ
1.170 (29.72)
(PINS DOWN)
0.010 (0.254)
26
30°
44
43
27
0.060 (1.52)
0.050 (1.27)
0.040 (1.02)
0.020 (0.508)
DETAIL A
ROTATED 90° CCW
DETAIL A
0.175 (4.45)
MAX
0.055 (1.40)
0.050 (1.27)
0.045 (1.14)
0.020 (0.508)
0.017 (0.432)
0.014 (0.356)
CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
012908-A
0.050 (1.27)
Figure 35. 68-Lead Ceramic Leaded Chip Carrier [CLCC]
(ES-68-1)
Dimensions shown in inches and (millimeters)
ORDERING GUIDE
Model1
AD10465BZ
5962-9961601HXA
1
2
Temperature Range2
−40°C to +85°C
−40°C to +85°C
Package Description
68-Lead Ceramic Leaded Chip Carrier [CLCC]
68-Lead Ceramic Leaded Chip Carrier [CLCC]
The data sheet for the 5962-9961601HXA is the property of and maintained by DSCC.
Case temperature.
©2001–2015 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D02356-0-7/15(B)
Rev. B | Page 24 of 24
Package Option
ES-68-1
ES-68-1
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